as depicted in fig2 , the input signal is an analog waveform containing the video to be displayed on the pixel array matrix . it has been stripped of synchronization and other control information which is used separately to ensure the appropriate sequencing of the row and column select pulses . the sequencing is used for application of video data to the pixel array in a raster pattern . as the input signal ( vin ) passes through the gamma correction circuit it is modified according to the nonlinear transfer function of the circuit shown in fig1 . the corrected signal ( vout ) is buffered by a unity gain voltage buffer ( v buffer ) in order to drive the total parasitic load capacitance of the column line within the allotted write cycle time . a copy of the output signal ( vout ) is stored in the selected pixel storage capacitor 10 . a unity gain buffer stage in the pixel forces the anode of the oled to the vout level and maintains this level until it is updated in the next write cycle . the oled current is a nonlinear function of its voltage level . however , since the gamma correction function is an exact inverse of the oled function , the final operating oled current will be linearly dependent on the input signal . the gamma correction oled pixel drive circuit of the present invention is illustrated in fig1 . the input signal ( vin ) is applied to the negative input of an operational amplifier 12 . the output of operational amplifier 12 drives the gate of a first pmos transistor 14 so that the voltage across the resistor 16 , connected between the output circuit of transistor 14 and ground , is essentially equal to the input signal ( vin ). as a consequence , the current flowing through the resistor 16 will be equal to vin / r . as the input voltage ( vin ) changes , the gate voltage across transistor 14 will track to maintain a current through transistor 14 that is linearly dependent on the input voltage ( vin ). the gate voltage at transistor 14 is simultaneously applied to the second pmos transistor 18 . if the dimensions of transistor 18 ( width and length ) are identical to those of transistor 14 , then the same current will flow through both devices . this ensures that the current through the oled reference device 20 , will be linearly dependent on the input signal ( vin ) as scaled by the resistence r of resistor 16 . the resistence r of resistor 16 is chosen to ensure that the current density through the reference oled device 20 is the same as the pixel oled for the chosen control range of the input voltage ( vin ). the output voltage ( vout ) is the voltage across the pixel oled ( not shown ) that corresponds to its current level as determined by its nonlinear iv characteristic . reference oled device 20 is connected between the output circuit of transistor 18 and the bias voltage ( v common ) for the pixel oleds . as a result , the vout / vin transfer function for the processing circuit of fig1 is exactly the inverse of the pixel oled current to voltage relationship . since the gamma correction function and the oled drive function are obtained from devices on the same chip , under similar operating conditions , the final linearity of the composite signal is well matched . the gamma reference circuit by itself will not provide sufficient speed to drive the column array due to its low operating current and consequent low bandwidth . to overcome this limitation , the circuit can be included in a high - speed feedback loop or it may be used as a static reference for an approximately equivalent nonlinear circuit , as shown in fig3 . an arbitrary piece - wise linear function generator provides the gamma correction functionality to a degree of accuracy determined by the number of linear segments used . each linear segment is defined by its pwl coefficients ( breakpoint and slope ). in this manner , the gamma reference circuit is used only to generate the pwl coefficients , which can be done as slowly as needed as these are effectively dc parameters . an example of a two - segment pwl function implementation is given in fig4 to illustrate the basic principle . the coefficients v 1 , a 1 , and b 2 are dc values which are easily provided by the gamma reference circuit in combination with standard operational function blocks . these parameters set the slopes and intercepts of the two gain blocks which form the two linear segments shown on the right in the figure . the input signal is compared to the first breakpoint v 1 by the comparator which controls a pair of transmission gates . if vin is less than v 1 , then the top transmission gate is closed and the bottom one is open , allowing the signal from the top gain block to appear at the output . when the input exceeds v 1 , the comparator reverses the states of the transmission gates and allows the signal from the lower gain block to pass to the output . this approach can be easily expanded to form a pwl function with any desired number of segments . many other circuit implementations are possible and do not affect the intended functionality of the invention . fig5 is a graphic representation of the relationship between the voltage input signal and voltage output signal for the circuit of fig4 . while only a limited number of preferred embodiments of the present invention have been disclosed for purposes of illustration , it is obvious that many modifications and variations could be made thereto . it is intended to cover all of those modifications and variations which fall within the scope of the present invention , as defined by the following claims :