although the present invention is explained mainly referring to a mcm system , it is obvious that the present invention can be used in connection with different signal transmissions that are based on different kinds of modulation . fig2 shows a mcm system overview on the basis of which the present invention will be described in detail . at 100 a mcm transmitter is shown that substantially corresponds to a prior art mcm transmitter except for the kind of the reference symbol being added to each frame of a mcm signal . a description of such a mcm transmitter can be found , for example , in william y . zou , yiyan wu , “ cofdm : an overview ”, ieee transactions on broadcasting , vol . 41 , no . 1 , march 1995 . a data source 102 provides a serial bitstream 104 to the mcm transmitter . the incoming serial bitstream 104 is applied to a bit - carrier mapper 106 which produces a sequence of spectra 108 from the incoming serial bitstream 104 . an inverse fast fourier transform ( fft ) 110 is performed on the sequence of spectra 108 in order to produce a mcm time domain signal 112 . the mcm time domain signal forms the useful mcm symbol of the mcm time signal . to avoid intersymbol interference ( isi ) caused by multipath distortion , a unit 114 is provided for inserting a guard interval of fixed length between adjacent mcm symbols in time . in accordance with a preferred embodiment of the present invention , the last part of the useful mcm symbol is used as the guard interval by placing same in front of the useful symbol . the resulting mcm symbol is shown at 115 in fig2 and corresponds to the mcm symbol 10 depicted in fig1 . signal transmitted through the channel 122 is received at the receiver front end 132 . the down - converted mcm signal is sampled at the receiver front end 132 and is , in the preferred embodiment , provided to a fast running automatic gain control ( time constant & lt ; mcm symbol duration ) in order to eliminate fast channel fluctuations ( channel coherence time = mcm symbol duration ). the fast agc 162 is used in addition to the normally slow agc in the signal path , in the case of transmission over a multipath channel with long channel impulse response and frequency selective fading . the fast agc adjusts the average amplitude range of the signal to the known average amplitude of the reference symbol . the so processed symbol is provided to an amplitude determining unit 164 . the amplitude determining unit 164 can use the simple alpha max + beta min − method in order to calculate the amplitude of the signal . this method is described for example in palachels a . : dsp - mp routine computes magnitude , edn , oct . 26 , 1989 ; and adams , w . t ., and bradley , j . : magnitude approximations for microprocessor implementation , ieee micro , vol . 3 , no . 5 , october 1983 . the output signal of the amplitude determining unit 164 is applied to a correlator 166 . in the correlator 166 , a cross correlation between the amplitude signal output from the amplitude determining unit 164 and a known ideal amplitude information is computed . the known ideal amplitude information is stored in the correlator . for both , the amplitude and the known ideal amplitude information , their amplitudes are symmetrically to zero relative to their average amplitude . in the ideal awgn case , the result will be a white noise signal with zero mean value and with a clearly visible positive maximum . in this ideal awgn case , the position of the single maximum is evaluated in a maximum position unit 172 . on the basis of this evaluation , the reference symbol and the guard intervals are extracted from the mcm signal in a combined reference symbol / guard extraction unit 136 / 138 . although these units are shown as a combined unit 136 / 138 in fig4 , it is clear that separate units can be provided . the mcm signal is transmitted from the rf front end 150 to the reference symbol / guard extraction unit 136 / 138 via a low pass filter 174 . in the case of time spreading encountered in a multipath channel , several maxima corresponding to the number of clusters in the channel impulse response occur in the output signal of the correlator . a schematic view of three such clusters located in a time window of maximum about 60 microseconds is shown in fig5 . out of the several maxima caused by the time spreading encountered in a multipath channel , the best one has to be selected as the position of the frame header , i . e . the reference symbol . therefore , a threshold unit 168 and a weighting unit 170 are provided between the correlator 166 and the maximum position unit 172 . the threshold unit 168 is provided to remove maxima having an amplitude below a predetermined threshold . the weighting unit 164 is provided in order to perform a weighting procedure on the remaining maxima such that the maximum corresponding to the reference symbol can be determined . an examplary weighting procedure performed in the weighting unit 170 is as follows . the first significant maximum is considered to be the best one . the output signal of the correlator is observed from the first detected maximum onwards for the maximum length of the channel impulse response and an amplitude weighting function is applied to the signal . because the actual channel impulse response length is unknown , the following fact can be remembered . during system design , the length of the channel impulse response has to be investigated . in a mcm system , the guard interval shall be equal or longer than the maximum expected channel impulse response . for this reason , the part ( interval with l i samples , l i corresponding to the maximum expected channel impulse response , i . e . the guard interval length ) of the correlation output signal starting with the first maximum , i k0 ( n )= r ( k 0 + n ), 0 ≦ n ≦ l i − 1 ( eq . 1 ) with k 0 being the position of the first maximum , will be examined to find the best frame start position . the above signal part is weighted with the function w ⁡ ( n ) = 10 - weight_db 10 ⁢ n l i - 1 ( eq . ⁢ 2 ) the position ( n max ) of the maximum in the resulting signal interval i k , ⁢ weighted ⁡ ( n ) = [ r ⁡ ( k 0 + n ) ⁢ w ⁡ ( n ) ] = [ r ⁡ ( k 0 + n ) ⁢ 10 - weight_db 10 ⁢ n l i - 1 ] ⁢ ⁢ 0 ≤ n ≤ l i - 1 ( eq . ⁢ 3 ) r ( k ) designates the output signal of the correlator ( 166 ) at the time k . the signal is present with a clock frequency which is determined by the multiplication : oversampling factor * subcarrier symbol frequency . the parameter k designates the discrete time in sample clocks . this signal is windowed with information from the threshold unit 168 . an interval having the length of l i values is extracted from the signal r ( k ). the first value being written into the interval is the correlation start value at the time k 0 , at which the output value r ( k 0 ) exceeds the threshold value of the threshold unit 168 for the first time . the interval with the windowed signal is designated by the term i ( k 0 ). the parameter n designates the relative time , i . e . position , of a value inside the interval . using the described weighting operation , the earlier correlation maxima are more likely to be chosen as right frame start position . a later coming maximum will only be chosen as frame start position , if the value of the maximum is significantly higher than the earlier one . this operation is applicable especially for mcm , because here it is better to detect the frame start positions some samples too early than some samples too late . positioning the frame start some samples too early leads to positioning the fft window a little bit into the guard interval , this contains information of the same mcm symbol and therefore leads to little effects . if the frame start position is detected some samples too late , then the fft window includes some samples of the following guard interval . this leads to a more visible degradation , because the following guard interval contains information of the following mcm symbol ( isi occurs ). it is important to know that the first visible correlation maximum after receiver power - on does not necessarily correspond to the first cir ( channel impulse response ) cluster . it is possible that it is corresponding to a later cluster , see fig5 . for this reason during power - on one should wait for a second frame start before starting demodulation . it is clear that amplitude determining methods different from the described alpha max + beta min − method can be used . for simplification , it is possible to reduce the amplitude calculation to a detection as to whether the current amplitude is above or below the average amplitude . the output signal then consists of a − 1 /+ 1 sequence which will be correlated with a known bit sequence , also in − 1 /+ 1 values . this correlation can easily be performed using a simple integrated circuit ( ic ). in addition , an oversampling of the signal received at the rf front end can be performed . for example , the received signal can be expressed with two times oversampling . this oversampled signal is passed to a fast running agc to eliminate fast channel fluctuations before the amplitude of the signal is calculated . the amplitude information will be hard quantized . values larger than the mean amplitude , mean amplitude is 1 , will be expressed as + 1 , values smaller than the mean amplitude will be expressed as − 1 . this − 1 /+ 1 signal is passed to the correlator that performs a cross correlation between the quantized signal and the stored ideal amplitude values of the reference symbol : if k = 2 ( oversampling factor )* 2 ( interpolation factor )* 1 , 2 , 3 . . . 92 ( 92 for 184 reference symbol and interpolation factor 2 ) amp — sto ( k )= 0 , else , k & lt ;= 2 ( oversampling factor )* plary weighting procedure performed in the weighting unit 170 is as follows . the first significant maximum is considered to be the best one . the output signal of the correlator is observed from the first detected maximum onwards for the maximum length of the channel impulse response and an amplitude weighting function is applied to the signal . because the actual channel impulse response length is unknown , the following fact can be remembered . during system design , the length of the channel impulse response has to be investigated . in a mcm system , the guard interval shall be equal or longer than the maximum expected channel impulse response . for this reason , the part ( interval with li samples , li corresponding to the maximum expected channel impulse response , i . e . the guard interval length ) of the correlation output signal starting with the first maximum , i k0 ( n )= r ( k 0 + n ), 0 # n # l i − 1 ( eq . 1 ) with k 0 being the position of the first maximum , will be examined to find the best frame start position . the above signal part is weighted with the function w ⁡ ( n ) = 10 - weight_db 10 ⁢ n l i - 1 ( eq . ⁢ 2 ) the position ( n max ) of the maximum in the resulting signal interval i k0 , weighted ⁡ ( n ) = [ r ⁡ ( k 0 + n ) ⁢ w ⁡ ( n ) ] = [ r ⁡ ( k 0 + n ) ⁢ 10 - weight_db 10 ⁢ n l i - 1 ] ⁢ ⁢ 0 ⁢ ⁢ # ⁢ ⁢ n ⁢ ⁢ # ⁢ ⁢ l i ⁢ ⁢ ⁢ 1 ( eq . ⁢ 3 ) r ( k ) designates the output signal of the correlator ( 166 ) at the time k . the signal is present with a clock frequency which is determined by the multiplication : oversampling factor * subcarrier symbol frequency . the parameter k designates the discrete time in sample clocks . this signal is windowed with information from the threshold unit 168 . an interval having the length of l i values is extracted from the signal r ( k ). the first value being written into the interval is the correlation start value at the time k 0 , at which the output value r ( k 0 ) exceeds the threshold value of the threshold unit 168 for the first time . the interval with the windowed signal is designated by the term i ( k 0 ). the parameter n designates the relative time , i . e . position , of a value inside the interval . using the described weighting operation , the earlier correlation maxima are more likely to be chosen as right frame start position . a later coming maximum will only be chosen as frame start position , if the value of the maximum is significantly higher than the earlier one . this operation is applicable especially for mcm , because here it is better to detect the frame start positions some samples too early than some samples too late . positioning the frame start some samples too early leads to positioning the fft window a little bit into the guard interval , this contains information of the same mcm symbol and therefore leads to little effects . if the frame start position is detected some samples too late , then the fft window includes some samples of the following guard interval . this leads to a more visible degradation , because the following guard interval contains information of the following mcm symbol ( isi occurs ). it is important to know that the first visible correlation maximum after receiver power - on does not necessarily correspond to the first cir ( channel impulse response ) cluster . it is possible that it is corresponding to a later cluster , see fig5 . for this reason during power - on one should wait for a second frame start before starting demodulation . it is clear that amplitude determining methods different from the described alpha + beta min − method can be used . for simplification , it is possible to reduce the amplitude calculation to a detection as to whether the current amplitude is above or below the average amplitude . the output signal then consists of a − 1 /+ 1 sequence which will be correlated with a known bit sequence , also in − 1 /+ 1 values . this correlation can easily be performed using a simple integrated circuit ( ic ). in addition , an oversampling of the signal received at the rf front end can be performed . for example , the received signal can be expressed with two times oversampling . this oversampled signal is passed to a fast running agc to eliminate fast channel fluctuations before the amplitude of the signal is calculated . the amplitude information will be hard quantized . values larger than the mean amplitude , mean amplitude is 1 , will be expressed as + 1 , values smaller than the mean amplitude will be expressed as − 1 . this − 1 /+ 1 signal is passed to the correlator that performs a cross correlation between the quantized signal and the stored ideal amplitude values of the reference symbol : if k = 2 ( oversampling factor )* 2 ( interpolation factor )* 1 , 2 , 3 . . . 92 ( 92 for 184 reference symbol and interpolation factor 2 ) * 2 ( interpolation factor )* 92 ( first part of amp — sto =[ 0 0 0 − 1 0 0 0 1 0 0 0 1 0 0 0 − 1 0 . . . ]). again , the maxima in the correlator output signal correspond to different frame start positions due to different multipath clusters . in this signal with various maxima the best frame start position has to be chosen . this is done in the following steps : the output of the correlator is given to a threshold detection . if the signal first time exceeds the threshold ( a threshold of 50 has proved to be applicable ) the best position search algorithm is initialized . the correlator output signal in the interval following the threshold exceeding value will be weighted with the weighting function , see above . the position of the resulting maximum in the weighted signal will be chosen as best frame start position . with the knowledge about the best frame start position the guard interval extraction and the following mcm demodulation will be performed . some more efforts can be carried out to increase frame synchronization accuracy . these methods will be explained in the following . a postprocessing of the frame start decision is performed in order a ) to increase the reliability of the frame synchronization ; b ) to secure that no frame start position is disregarded ; and c ) to optimize the frame start position in case of varying cir cluster positions . using information of other frame start positions . it is known that in front of each frame a reference symbol is inserted into the signal . if the position of the currently detected frame start has changed significantly regarding the last detected frame start , demodulation of the two frames in total and completely independent from each other is possible . it is also possible to buffer the last signal frame and to perform the required shift of the frame start position step by step with the mcm symbols of the frame . this results in an interpolative positioning of the single mcm symbols including simultaneous asynchronous guard interval extraction for the different mcm symbols . such an interpolative positioning of the fft window is also possible if one frame start position is missing , i . e . the frame start has not been detected . if one frame start position is missing the guard interval extraction can be performed the same way as in the frame before without large performance degradation . this is due to the normally only slowly varying cir cluster positions , but only if the signal strength is good enough . stopping demodulation and waiting for the next detected frame start position is also imaginable but not desirable because of the long interrupt . what follows is an example of a reference symbol of 184 samples ( subcarrier symbols ) as provided by the inventive apparatus for generating a signal having a frame structure . this modulated binary sequence i — q is interpolated in order to produce an interpolated sequence i — q — int : amp — int is the reference symbol inserted periodically into the signal after the guard interval insertion . as it is clear from the above specification , the present invention provides methods and apparatus for generating a signal having a frame structure and methods and apparatus for frame synchronization when receiving such signals which are superior when compared with prior art systems . the frame synchronization algorithm in accordance with the present invention provides all of the properties shown in table 1 in contrary to known frame synchronization procedures . table 1 shows a comparison between the system in accordance with the present invention using an am sequence as reference symbol and prior art systems ( single carrier and mcm eureka 147 ). as can be seen from table 1 different synchronization tasks and parameters can be derived using the frame synchronization with an am sequence in accordance with the present invention . the frame synchronization procedure mcm eureka 147 corresponds to the procedure described in u . s . pat . no . 5 , 191 , 576 .