fig1 shows an angle sensor 8 with a rotor 2 of a brushless electric motor on which a rotatable element 3 for varying a field is arranged . the rotatable element 3 is embodied here as a dipole magnet , wherein the north pole n and the south pole s are shown . depending on the rotational angle α of the rotor 2 relative to the brushless electric motor , a first linearly independent vector 15 of the field strength denoted here by h x , and a second linearly independent vector 16 of the field strength , denoted here by h y , are induced in the sensor chip 9 of the angle sensor 8 . these vectors 15 , 16 are generated by a magnetic field and are strictly dependent on the rotational angle α and the associated position of the rotatable element 3 . the first sensor element 4 , embodied as a vertical hall element , and the second sensor element 5 , embodied as a vertical hall element in the sensor chip 9 , senses the components of the first linearly independent magnetic field vector 15 and of the second linearly independent magnetic field vector 16 . the absolute value of the linearly independent magnetic field vectors 15 and 16 is particularly highly dependent on the distance d between the plane in which the first sensor element 4 and the second sensor element 5 are arranged and the plane in which the rotatable element 3 rotates in order to vary the magnetic field . if the distance d between the rotatable element 3 and the sensor chip 9 on which the first sensor element 4 and the second sensor element 5 are arranged becomes smaller , relatively high hall voltages are generated in the sensor elements 4 , 5 , and if the distance d between the rotatable element 3 and the sensor chip 9 becomes larger , significantly lower hall voltages are generated in the first sensor element 4 and the second sensor element 5 . as a result , the uncontrolled output signals of the first sensor element 4 and of the second sensor element 5 become partially unusable for the further signal processing since they are either too small in order to utilize the full resolution of an analog / digital converter , or are so large that , for example , an analog / digital converter is overdriven , wherein part of the signal is cut off . the situation will be explained in more detail below in fig2 a . fig2 shows the sine - shaped and cosine - shaped output signals of the first sensor element 4 and of the second sensor element 5 with a constant distance d between the rotatable element 3 and the sensor chip 9 that forms the plane in which the first sensor element 4 and the second sensor element 5 are arranged . in fig2 , clean sine profiles and cosine profiles can be seen for the hall voltage u hall , which permit unambiguous resolution of the rotational angle α of between − 180 ° and + 180 °, and as a result of which the full circle can be completely and clearly sensed by the angle sensor 8 specified here . fig2 a shows the output signal of the first sensor element 4 or of the second sensor element 5 for different distances d , d 1 , d 2 between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 . the optimum distance is denoted here by d , a distance smaller than the optimum one is denoted by d 1 , and a distance larger than the optimum one between the rotatable element 3 and the plane of the first sensor element and of the second sensor element 5 is denoted by d 2 . for the sake of simplicity , only the sine profile of the signal of the first sensor element 4 is illustrated in fig2 a , wherein the cosine profile of the signal of the second sensor element 5 would behave in an analogous fashion . given an optimum distance d between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 , the already known sine function , which is characterized by the reference symbol d in fig2 a , is obtained . if the distance between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 is then increased , a significantly flatter profile of the sine function , characterized in fig2 a by the reference symbol d 2 , is thus obtained . since the analysis of the signals supplied by the angle sensor 8 is generally carried out by an analog / digital converter , a large dynamic range of the analog / digital converter would remain unused as a result of the very flat profile of the sine curve , and the measurement results are therefore degraded since a relatively small range of digital values also permit a smaller resolution to be achieved . given a significant reduction in the distance d 1 between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 , the situation characterized by d 1 in fig2 a would come about . the sine signal which can be seen here is cut off at cutoff voltage u g since the subsequent analog / digital converter is overdriven , as a result of which no resolution at all of the rotational angle of the rotor 2 can be achieved any more in wide rotational angle ranges . both the increased distance d 2 and the reduced distance d 1 between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 lead to very poor measurement results which are not acceptable within the scope of application of the angle sensor 8 in automobile technology . fig3 shows an angle sensor 8 based on the principle of electromagnetic induction of a field in the first sensor element 4 and the second sensor element 5 . the sensor elements 4 , 5 are embodied as coil arrangements , for example on a printed circuit board 9 . the rotatable element 3 is designed here to vary an electromagnetic field and is connected to the rotor 2 of the brushless electromotor 1 . when the rotatable element 3 rotates , the electromagnetic field is sensed by the first sensor element 4 and the second sensor element 5 , embodied here as a pair of coils on a sensor printed circuit board 9 . in an integrated circuit 21 on the sensor printed circuit board 9 there are the analysis electronics for the signals of the first sensor element 4 and the second sensor element 5 . these analysis electronics are composed of amplifiers 10 , controlled amplifiers 11 , which are also referred to as operational amplifiers , low - pass filters 12 , high - pass filters 13 and inverters 14 . fig4 shows the design of a 2 - d hall element known in principle from fig1 expanded by a third dimension to form the 3 - d hall element . located on the sensor chip 9 are the first sensor element 4 and the second sensor element 5 which form , with the sensor chip 9 , the plane in which the magnetic field induced by the element 3 in order to vary the magnetic field , is measured . the element 3 for varying the magnetic field is embodied here as a permanent magnet with a north pole n and south pole s . furthermore , there is a third sensor element 6 , as a result of which the sensor chip 9 shown here is expanded to what is referred to as a 3 - dimensional hall element ( 3 - d hall element ). furthermore , a temperature sensor element 7 is integrated into the sensor chip 9 . this temperature sensor element 7 measures the temperature prevailing in the angle sensor 8 . changes in temperature in the angle sensor 8 , in particular in the sensor elements 4 , 5 and 6 , can lead to a massive change in the signals generated by the sensor elements 4 , 5 and 6 . the method for analyzing signals of an angle sensor 8 having at least two sensor elements 4 and 5 which span a plane and having a rotatable element 3 which is spaced apart from this plane and has the purpose of varying the field will be explained in more detail in the following figures . in fig5 , the sensor elements 4 and 5 sense at least a first and a second vector 15 and 16 , independent of one another , of the field h x , h y in this plane . in addition , a third vector 17 which is linearly independent of the first and second vectors 15 and 16 and which represents the absolute value of the field h z in the z direction , is sensed , wherein this absolute value is dependent on the distance d between the plane and the rotatable element 3 , and wherein the amplitude of the signals of the sensor elements 4 and 5 is controlled with this absolute value . the first sensor element 4 and second sensor element 5 are arranged here in the plane of the sensor chip 9 . the magnetic field vectors 15 and 16 which are sensed by the first sensor element 4 and the second sensor element 5 are as electric signals to the controllable amplifiers 11 . these controllable amplifiers 11 are generally embodied as operational amplifiers . since the signals which are sensed by the first sensor element 4 and the second sensor element 5 are greatly dependent on the distance d between the rotatable element 3 and the plane of the sensor chip 9 , the distance d is sensed by the third sensor element 6 , which measures the z component of the magnetic field h z here . the signal which is sensed by the third sensor element 6 is fed via a first amplifier 10 and a low - pass filter 12 , which filters away high - frequency signals to an analog inverter 14 , as a result of which control variables for the controllable amplifiers 11 are available here with which the signal strength of the distance d , d 1 , d 2 between the rotatable element 3 and the plane of the sensor chip is tracked in a manner corresponding to the first sensor element 4 and the second sensor element 5 . these corrected signals from the first sensor element 4 and the second sensor element 5 are then made available to analog / digital converters , which can therefore always operate in the full range of their resolution and bandwidth without being overdriven in this instance . furthermore , in this method , the temperature t of the temperature sensor element 7 is sensed , which temperature prevails within the angle sensor 8 . this temperature measurement value can also be included by means of an amplifier 10 in the correction of the signals from the first sensor element 4 and from the second sensor element 5 . as a result of the method according to the invention , a complete correction of distance fluctuations and temperature fluctuations within the angle sensor 8 is possible , as a result of which full - circle - coverage angle sensor elements can be used cost - effectively within the scope of automobile applications . furthermore , fig5 shows a high - pass filter 13 . the available signals are illustrated . on the basis of the signal from the third sensor element 6 it is possible , after amplification 10 and high - pass filtering 13 , to detect a rapid change in distance between the rotatable element 3 and the sensor chip 9 . this rapid change in distance would provide , for example , an indication of a defective bearing of the rotor 2 in the brushless electric motor 1 . the low - pass filtering 12 of the signal from the third sensor element 6 generates a signal for a slow change in distance d between the rotatable element 3 and the plane of the sensor chip 9 . this slow change in distance can be triggered by temperature expansion of the overall system . fig6 shows a further refinement of the invention . here , the further variable 17 , dependent on the distance d , d 1 , d 2 , is derived from the first and second vectors 15 , 16 which are linearly independent of one another and which are sensed by the sensor elements 4 , 5 . for this purpose , for example the resulting absolute value of the first and second linearly independent vectors 15 , 16 are formed by pythagoras &# 39 ; s theorem in a computational circuit 19 . the absolute values of the individual linearly independent vectors 15 , 16 , which are represented chronologically as sine signals and cosine signals , are larger when there is a relatively small distance d 1 between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 , and become smaller as the distance increases . as a result , the computation circuit 19 can supply largely angle - independent information about the distance d between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 . fig7 shows a subsequent refinement of the invention . the further variable 17 which is dependent on the distance the distance d between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 is derived here from the supply current 20 for operating the inductive sensor elements 4 , 5 . for the inductive measuring method , an electromagnetic alternating field is generated , as a result of which an eddy current is induced in the rotatable element 3 . the absolute value of the eddy current rises as the distance d becomes smaller and falls as the distance d becomes larger . the absolute values of the linearly independent vectors 15 , 16 in their chronological representation as sine signals and cosine signals also become larger as the distance d 1 becomes smaller and fall as the distance d 2 becomes larger . the computational circuit 19 can therefore also provide largely angle - independent information about the distance d between the rotatable element 3 and the plane of the first sensor element 4 and of the second sensor element 5 . the representation of a possible overall system is found in fig8 . here , a brushless electromotor 1 is illustrated with a rotor 2 , wherein the rotatable element 3 for varying a magnetic field is arranged on the rotor 2 . in accordance with the rotational angle α , the rotatable element 3 will induce a characteristic magnetic field in the sensor chip 9 . this characteristic magnetic field is picked up by the first sensor element 4 , the second sensor element 5 and the third sensor element 6 . the distance between the rotatable element 3 and the sensor chip 9 can vary , which is represented by the reference symbols d 2 , d 1 and d 0 here . this variation in the distance d between the rotatable element 3 and the plane in which the first sensor element 4 and the second sensor element 5 are arranged is sensed by the third sensor element 6 by the magnetic field component h z . as a result , the third sensor element 6 provides a correction value h z that is fed to the controllable amplifiers 11 via the first amplifier 10 and a low - pass filter 12 as well as an inverter 14 . the magnetic field values h y and h z are sensed by the first sensor element 4 and the second sensor element 5 , as a result of which the first sensor element 4 acquires a first linearly independent vector 15 and the second sensor element 5 senses a second linearly independent vector 16 . the angle α can be inferred clearly by a cordic algorithm on the basis of the combination of these two linearly independent vectors . the distance dependence between the rotatable element 3 and the sensor chip 9 is corrected in the controllable amplifiers 11 , as a result of which a clear resolution , which is high in terms of measuring technology , of the 360 ° full circle is possible with the angle sensor 8 illustrated here . thus , while there have shown and described and pointed out fundamental novel features of the invention as applied to a preferred embodiment thereof , it will be understood that various omissions and substitutions and changes in the form and details of the devices illustrated , and in their operation , may be made by those skilled in the art without departing from the spirit of the invention . for example , it is expressly intended that all combinations of those elements and / or method steps which perform substantially the same function in substantially the same way to achieve the same results are within the scope of the invention . moreover , it should be recognized that structures and / or elements and / or method steps shown and / or described in connection with any disclosed form or embodiment of the invention may be incorporated in any other disclosed or described or suggested form or embodiment as a general matter of design choice . it is the intention , therefore , to be limited only as indicated by the scope of the claims appended hereto .