fig3 shows a floating capacitive structure fabricated by a conventional mos fabrication process , as taught by the present invention . a capacitive circuit 301 includes pmos devices 302 and 303 , fabricated on a p - type substrate . the source , drain , and body terminals of devices 302 and 303 are all connected together to form a bias terminal 305 . a biasing circuit 304 is connected to bias terminal 305 . the gate terminals of devices 302 and 303 provide the input and output terminals of the capacitive structure . while devices 302 and 303 are shown as pmos devices , it will be apparent to those skilled in the art that nmos devices fabricated on an n - type substrate could also be used in the present invention . it should also be noted that pmos devices on an n - type substrate and nmos devices on a p - type substrate could also be utilized . however , in those cases the body terminal would be the substrate itself -- no n - well or p - well , respectively -- making such implementations more susceptible to noise from adjacent circuitry . capacitive circuit 301 can be modeled by schematic circuit 400 of fig4 . capacitances c402 and c403 are the mos capacitances of fet devices 302 and 303 , respectively . capacitances c404 and c405 are the parasitic capacitances of fet devices 302 and 303 , respectively . in this embodiment of the present invention , parasitic capacitances c404 and c405 are located away from capacitive circuit 301 &# 39 ; s input and output terminals , minimizing any effects on the input and output signals . therefore , the effective capacitance , ceff , of capacitive circuit 301 is given by the following : fig5 shows an embodiment of biasing circuit 304 integrated with capacitive circuit 301 . a current generator 502 includes a pmos device 504 . the circuit power supply voltage vdd is applied to the drain terminal of device 504 . a predetermined voltage vref is input to the gate of device 504 , which sources a reference current iref . nmos device 505 in current mirror 503 accepts current iref , which is mirrored by scaled nmos device 506 as a bias current ibias . by adjusting the channel length of device 506 relative to that of device 505 , the ratio of ibias to iref is set . this ratio is defined such that ibias is several orders of magnitude smaller than iref , in order to make device 506 operate at very low current . as ibias approaches zero , device 506 behaves like a large resistor . quiescent current flow through current generator 502 and current mirror 503 is minimized through adjustment of reference voltage vref to produce a small iref . the drain terminal of device 506 connected to bias terminal 305 . because device 506 is operating within its linear regime , it acts as a high - impedance resistor to ground , biasing bias terminal 305 to ground , even when ibias equals zero . at this point , capacitive circuit 301 provides constant capacitance as long as both devices 302 and 303 are operating in their respective saturation regimes . therefore , device 302 and device 303 must each satisfy the relationship : where vsdb is the bias voltage applied to bias terminal 305 , and vt and vg are the threshold voltage and the gate terminal voltage , respectively , of either device 302 or device 303 . vsdb , which is determined by current generator 502 and current mirror 503 , is at ground , so capacitive structure 301 provides constant capacitance as long as the gate terminal voltages of devices 302 and 303 are both in the range between their respective threshold voltages and the power supply voltage of the circuit , vdd . fig6 is another embodiment of biasing circuit 304 , integrated with capacitive circuit 301 . a current generator 602 includes an nmos device 604 . a predetermined voltage vref is input to the gate of device 604 , which sinks a reference current iref from the source terminal of pmos device 605 in current mirror 603 . this reference current iref is then mirrored by matched pmos device 606 as a bias current ibias . by adjusting the channel length of device 606 relative to that of device 605 , the ratio of ibias to iref is set . this ratio is defined such that ibias is several orders of magnitude smaller than iref , in order to make device 606 operate at very low current . as ibias approaches zero , device 606 behaves like a large resistor . quiescent current flow through current generator 602 and current mirror 603 is minimized through adjustment of reference voltage vref to produce a small iref . the drain terminal of device 606 is connected to bias terminal 305 . because device 606 is operating within its linear regime , it acts as a high - impedance resistor to vdd , biasing bias terminal 305 high , even when ibias equals zero . at this point , capacitive circuit 301 provides constant capacitance as long as both devices 302 and 303 are operating in their respective saturation regimes . therefore , devices 302 and 303 must each satisfy the relationship : where vsdb is the bias voltage applied to bias terminal 305 , and vt and vg are the threshold voltage and the gate terminal voltage , respectively , of either device 302 or device 303 . vsdb is determined by current generator 602 and current mirror 603 , and is at vdd . therefore , capacitive structure 301 provides constant capacitance while the gate terminal voltages of devices 302 and 303 fall within the following range : where vg30x and vt30x refer respectively to the gate voltage and threshold voltage of each device . the above - described embodiments of the present invention are merely meant to be illustrative of the present invention and not intended to be limiting . it will thus be apparent to those skilled in the art , upon consideration of the above detailed description and drawings , that various changes and modifications may be made within the scope of the present invention . for example , nmos devices could be incorporated into the embodiments of the present invention where pmos devices were described , and vice versa . also , the bias circuit could be implemented an any manner that provides a high - impedance output or a low current leakage path , such as a transistor network . finally , any circuit for a current source , such as a cascode current source , and for a current mirror , such as a wilson current mirror , could be used instead of the previously described circuits . therefore , the appended claims encompass all such changes and modifications as fall within the scope of this invention .