referring to fig2 there is shown a block level diagram of a non - volatile memory device 50 of the present invention . in the embodiment shown in fig2 , the memory device 50 comprises two arrays 52 a and 52 b of non - volatile memory cells 10 of the type shown in fig1 , arranged in a plurality of rows and columns in a semiconductor substrate 12 . adjacent to each array 52 of non - volatile memory cells 10 is a decoder ( xdecoder 54 a and 54 b , respectively ), for receiving address signals to be decoded and supplied to the word lines 22 of selected and unselected memory cells 10 . each of decoders 54 also has an associate negative charge pump included in a charge pump 56 to generate a negative voltage . a decoder ( wshdrhalfv , ncg ) 80 placed in between the array 52 a and 52 b provides voltage levels for the control gate 26 , the sourceline 14 , and the erase gate 28 as shown in embodiments in fig5 - 7 . each of the memory arrays 52 of the memory device 50 also has a plurality of sensors 58 associated therewith to receive the signals from the memory cells 10 from the array 52 and to generate output signals from the device 50 . the memory device 50 also has a logic circuit 60 . the logic circuit 60 receives commands such as program , erase or read issue by a host controller ( not shown ), external to the memory device 50 to cause the memory device 50 to execute the various commands . in response to the commands received , the logic circuit 50 generates control signals that control the operation and the timing of the charge pump circuits 56 and the decoding circuits 54 , and sense amplifier circuits 58 . the analog circuit 70 provides analog bias voltages and currents and timing for the device 50 . a high voltage ( positive , negative ) control circuit 90 provides regulated and time - sequenced positive and negative levels . a pad circuit 88 provides input buffers , io buffers , power pads ( vdd , vss ), test pads , and esd protection . in response to the read , erase or program command , the logic circuit 60 causes the various voltages to be supplied in a timely and least disturb manner to the various portions of both the selected memory cell 10 and the unselected memory cells 10 . for the selected and unselected memory cell 10 , the voltage and current applied are as follows . as used hereinafter , the following abbreviations are used : source line or first region 14 ( sl ), bit line 20 ( bl ), word line 22 ( wl ), coupling gate 26 ( cg ), erase gate 28 ( eg ). alternatively , the erase operation can be performed with p substrate 12 being negative instead of 0v , e . g ., vsub =− 6v , in this case , the voltage on the wordline wl 22 is =& lt ;− 4v ( to prevent wl oxide breakdown ). alternatively , the program command can be performed with the following voltages and current : alternatively , the program operation can be performed with the p substrate vsub 12 being negative instead of 0v , e . g ., − 1v to − 5v , in this case , the voltage on the selected wordline wl 22 is such that ( vwl − vsub )˜=& lt ; 2v , i . e ., vwl ˜=& lt ; 1v to − 3v ( to prevent wl oxide breakdown ). referring to fig3 a there is shown one example of a signal timing waveform for program and erase signals for positive / negative bias levels as described above for use in the memory device 50 of the present invention . signals wl , bl , cg , eg , sl as corresponding respectively to terminals wl , bl , cg , eg , sl of the memory cell 10 are as described above . for programming , a signal wl 102 goes to high ( e . g ., ˜ vdd ) first ( such as to set control signal in the decoder circuit 80 to be described later ) then start to settle down ( to a bias voltage vpwl ). then signal bl 104 and cg 106 goes high , e . g ., ˜ vinh =˜ vdd and 10 to 11v respectively , and then eg and sl 110 goes high ( e . g , ˜ 4 . 5v to 5v ). alternatively cg 106 goes high after eg 108 and sl 110 ( as shown by the dotted line waveform ). the signal wl 102 settles down to a voltage vpwl , e . g , 1v , and the signal bl 104 settles down to a voltage vdp , e . g ., ˜ 0 . 5v as cg goes high . unselected wls goes down to negative , e . g ., − 0 . 5v , before or concurrent with selected wl 102 goes high . unselected cgs , egs , stays at value in standby , e . g , 0 to 2 . 6v . unselected sls stays at a value in standby , e . g ., 0v or switches to a bias voltage , e . g ., 1v , as cg 106 goes high ( unselected sl switching to a bias level to prevent leakage current through unselected cells through the bls ). the signal bl 104 goes first high to vinh ( inhibit voltage ) to prevent inadvertent program disturb due various signals are not settled yet during ramping to programming voltages . the timed sequence cg 106 vs . eg 108 and sl 110 are optimized to reduce disturb effect , e . g . whichever signal causes more disturb goes high last . the ramping down of programming pulses are reversed in order to minimize disturb ( i . e ., signal that goes up first now goes down last ). the signals eg 108 , sl 110 goes down , then cg 106 goes down , then wl 102 and bl 104 goes down . in the embodiment of programming with the substrate p going negative , e . g ., − 1v , this negative switching is concurrent with the signal wl goes low or the cg or eg goes high . for erase , the signal wl 102 goes high , e . g , vdd , ( such as to set control signal in the decoder circuit 80 to be described later as embodiments in fig5 - 7 ) then goes low , e . g , 0v ( or alternatively a negative such as − 0 . 5v ). at approximately same time as the wl 102 going low , the signal cg 106 goes negative , e . g , − 6v to − 9v , then the signal eg 108 goes high , e . g ., 8 to 9v . the signals bl 104 , sl 110 stays at a value in standby , e . g ., 0v . alternatively the signal cg 106 goes negative after eg 108 goes high . unselected wls goes down to negative , e . g ., − 0 . 5v , before or concurrent with selected wl 102 going high . unselected cgs , egs , stay at value in standby , e . g , 0 to 2 . 6v . unselected sls stay at a value in standby , e . g ., 0v . in the embodiment of erase with the substrate p going negative , e . g ., − 6v , this negative switching is concurrent with the signal wl goes low . this is to prevent stressing or breakdown of the wl gate oxide . the ramping down of erase pulses is approximately reversed in order ( i . e ., signal that goes up first now goes down last ). the signals eg 108 goes to standby value , e . g ., 0v , then cg 106 goes to standby value , e . g ., 0v . referring to fig3 b there is shown one example of a signal timing waveform for read signals for positive / negative bias levels as described above for use in the memory device 50 of the present invention . this read signal waveform goes with the program and erase signal waveform in fig3 a for complete non - volatile erase / program / read operation . for read normal waveform , the sl 110 is at standby value , e . g ., 0v . the cg 106 is at standby value , e . g ., 0v or 2 . 6v , or alternatively switching to a bias value in read , e . g . 2 . 6v ( to help increase the memory cell current due to cg voltage coupling to fg potential in read condition ). the eg 106 is at standby value , e . g ., 0v or 2 . 6v , or alternatively switching to a bias value in read , e . g . 2 . 6v ( to help increase the memory cell current due to eg voltage coupling to fg potential in read condition ). the standby values are similar to those for program and erase condition . the wl 102 and bl 104 switch to bias level in read , e . g . 2 . 6v and 1 . 0v respectively to selected memory cells for reading . a read margin0 operation is performed after programming the whole array to detect weak programming cells . after programming , the cell current is at a very low value normally & lt ; nano amperes ( na ), this corresponds to reading out a ‘ 0 ’ digital value ( no cell current ). however some cells may marginally stay at a couple micro amperes ( due to weak programming due to various reasons such as cell leakage , weak cell programming coupling ratio , process geometrical effect , etc . . . . ) and this can causing read ‘ 0 ’ to fail during the operating lifetime of the memory device 50 . a read margin ° is used to screen out those weak cells . for read margin ° waveform , the sl 110 is at standby value , e . g ., 0v . the eg 106 is at standby value , e . g ., 0v or 2 . 6v , or alternatively switching to a bias value in read , e . g . 2 . 6v as same in read normal condition . the wl 102 and bl 104 switch to bias level in read , e . g . 2 . 6v and 1 . 0v respectively to selected memory cells for reading as in read normal condition . the cg 106 is biased at a margin0 value ( provided by same circuit means described in fig6 - 8 as for program or read condition ) in read , e . g . 3v , to detect weak programmed cells . the cg voltage will couple into fg potential to amplify the weak programming effect , effectively increase the cell current , so the weak cells now read as a ‘ 1 ’ instead of a ‘ 0 ’ ( effectively there is cell current instead of no cell current ). a read margin1 operation is performed after erasing the whole array to detect weak erased cells . negative cg now ( provided by same circuit means described in fig6 - 8 as for erasing with negative voltage ) is utilized to detect this condition . the sl 110 is at standby value , e . g ., 0v . the eg 108 is at standby value , e . g ., 0v or 2 . 6v , or alternatively switching to a bias value in read , e . g . 2 . 6v as same in read normal condition . the wl 102 and bl 104 switch to bias level in read , e . g . 2 . 6v and 1 . 0v respectively to selected memory cells for reading as in read normal condition . the cg 106 is biased at a margin1 value in read , e . g . − 3v , to detect weak erased cells . the cg voltage will couple negatively into fg potential to amplify the weak erased effect , effectively decrease the cell current ( less fg potential ), so the weak erased cells now read as a ‘ 0 ’ instead of a ‘ 1 ’ ( effectively there is no cell current instead of cell current ). referring to fig4 a there is shown one example of a circuit diagram of the xdecoder 200 for use in the memory device 50 of the present invention . the xdecoder circuit 200 provides the decoded address signals to be supplied to the word lines 22 of the selected and unselected memory cells 10 . the xdecoder circuit 200 operates in the following manner . nand gate 201 and inv 202 is used for decoding wordline ( row ) pre - decoded signal xpa - xpc ( which is called memory sector ( address ) selection ). circuit 280 consists of a pre - driver and a driver . pmos transistors 210 and 211 and nmos transistor 212 are wordline pre - driver combined with pre - decoded xpz & lt ; 0 : 7 & gt ;. pre - decoded signals xpz & lt ; 0 : 7 ) is used to select one row out of eight ( by being =‘ 0 ’). pmos transistor 213 and nmos transistor 214 are wordline wl driver , used to drive a memory row that includes typically 2048 or 4096 cells in a row and hence needing big size transistor for wordline rc delay , i . e ., large w / l ratio , w = transistor width and l = transistor length . the circuit 280 is repeated 8 times and nand 201 and inv 202 is repeated one time for 8 rows per memory sector size . typically the source of the transistor 214 is connected to a ground node ( i . e ., 0v ) for de - selection condition , here it is connected to a node nwllow 240 . the source of the transistor 213 is connected to a node zvdd 220 , which is equal to vwlrd ( read wordline voltage ) in read operation , equal to vpwl ( programming wordline voltage in programming operation ). for programming condition , for selected wordline , wl = zvdd = vpwl = 1 . 0v for example , for unselected wls = nwllow , which is equal to − 0 . 5v . for erase condition , for selected wordline wl and un - selected wls = nwllow =− 0 . 5v in one embodiment . for read condition , for selected wordline , wl = zvdd = vwlrd = 2v for example , for un - selected wordlines wls = nwllow , which is equal to − 0 . 5v in one embodiment . referring to fig4 b there is shown one example of a circuit diagram of a negative charge pump generator 260 ( which is part of the charge pump 56 that provides both negative and positive voltages ) for generating a negative voltage to be supplied to the word lines 22 . the negative charge pump circuit 260 operates in the following manner . in a first time period , pmos transistor 263 and nmos transistor 266 are used to charge (+) 268 and (−) terminal 269 of a capacitor 265 to a positive bias voltage nbias 267 and a ground level ( i . e ., 0v ) respectively . in a next time period after the first period , the transistor 266 is turned off and a nmos transistor 264 is turned on to discharge the (+) terminal 268 of the capacitor 265 from a bias level 268 to ground level . at this time , the (−) terminal 269 of the capacitor 265 will be capacitively coupled to a negative level , e . g ., − 0 . 5v , depending on value of the capacitor 265 to the capacitive loading at the node nwllow 240 . by adjusting level of nbias 267 and the value of the capacitor 265 , the negative level is adjusted . for the embodiment of a semiconductor process using p substrate = 0v ( grounded ) for forming the memory device 50 , e . g ., single well cmos ( p - substrate for n type devices and a single n well for p type devices ), the negative level is clamped at a p / n + forward junction forward bias (˜− 0 . 6v ). as is well known , the memory device 50 can be made of a twin well p - sub cmos process , in which two wells ( p well and n well ) are constructed in the substrate 12 . since the substrate 12 is of p type conductivity , a first p well therein would be for n type devices ( nmos ), and a second n type well would be for p type devices ( pmos ). the negative voltage charge pump generator 260 and the wordline decoder 200 can be made in a triple well in the substrate 12 . this is done by a triple well cmos process instead of the twin well p - sub cmos process described earlier . in that event , the negative pump generator 260 and the wordline decoder 200 would be made in a third p type well ( which is made in the second n type well , which is inside the substrate 12 ) and the second n type well . this third p type well can now be applied negative voltage which is advantageous in certain operating conditions . although constructing the memory device 50 having a triple well is more process intensive , the benefit of having the pump generator 260 and the wordline decoder 200 in a triple well is that the negative voltage applied to the word line 22 can be more negative , for example − 6 . 0v used for an erase embodiment , ( i . e . not clamped by the p / n + junction forward bias ˜− 0 . 6v ). in this case the third p type well voltage condition can be negative to avoid the p / n + junction forward bias , e . g , − 6 . 0v or − 8 . 0v or − 5 . 6v . in an embodiment the memory cell 10 can be formed in the third p type well . referring to fig5 there is shown a first embodiment of a high voltage decoding circuit 300 for positive / negative level signals for use in the memory device 50 of psub cmos process of the present invention . a circuit 320 consisting of hv ( high voltage , e . g . 12v ) pmos transistors 321 and 322 and hv nmos transistor 323 and lv ( low voltage , e . g ., 3v ) transistors 324 and 325 are used for decoding eg signal for erase / program / read operation . the transistor 322 ( eg current limiter ) is used to limit current in erase and / or program ( to limit current sinking from the hv charge pump ). a circuit 310 is a hv latch circuit used to enable the hv control for the sector ( 1 sector per 8 rows ) selected , which is selected once a wl signal is asserted (˜ vdd ) at the beginning of the erase or programming sequence as shown in fig3 a . a circuit 350 consisting of native hv nmos transistor 351 , inverter 352 , nand 353 , a lv latch ( consisting of inverter 354 and 355 and set lv nmos transistors 356 , 359 , 358 and reset lv nmos transistor 357 ) is used to disable the hv signal if the sector is bad sector ( not to be used ). a circuit 330 consisting of lv pmos transistors 331 and 332 and hv pmos transistor 333 is used to provide cg bias level in standby and read . the transistor 331 ( its gate is at a bias level ) acts as current limiter to cg terminal to limit current from bad cg terminal such as in standby condition . a circuit 340 consisting of hv pmos transistors 341 and 342 is used to provide cg bias level in erase / program . the transistor 341 could act as current limiter to cg terminal in erase / program to limit current supplied from hv chargepump . a circuit 360 consisting of hv pmos transistor 361 , hv native nmos transistor 362 , lv nmos transistors 363 and 364 is used to disable the cg . a circuit 370 consisting of hv pmos transistor 371 , hv nmos transistor 373 and lv nmos transistor 372 is used to enable sl signal for erase / program / read condition . the lv nmos transistor 372 is used to pulldown the sl to ground in read and erase and to a bias level , e . g . & lt ; 2v , in program . a circuit 380 is a negative decoding circuit for the cg signal . the circuit 360 uses pmos transistor 361 as isolation transistor to isolate negative level ( provided by the circuit 380 going into cg terminal of memory cell ) from the nmos transistor 362 for psub cmos process . the circuit 380 uses clocked negatively bootstrapped high voltage circuit scheme . the circuits 380 consists of pmos transistors 381 , 382 , 385 - 391 and nor 384 and inverter 384 . the nor 384 and inverter 384 is used to enable a clocking signal into the pmos transistors 386 and 388 which act as a capacitor to negatively pumping gate of the transistor 387 . the transistor 385 acts as a bootstrap transistor for the pmos transistor 387 and the pmos capacitors 386 and 388 . the transistors 381 / 390 and 382 / 391 serves to clamp the drain of the transistor 387 and the drain of the transistor 385 respectively at vdd level . the transistor 389 serves as a buffer for negative level into cg . the sources of transistors 385 and 387 connect to a negative power supply vcgneg 399 . referring to fig6 there is shown second embodiment of a high voltage decoding circuit 400 for positive / negative level signals for use in the memory device 50 of triple well cmos process of the present invention . the circuits 310 - 350 , 370 are same or similar as those of fig5 . a circuit 410 consisting of hv nmos transistor 410 and lv nmos transistors 412 - 414 is used for de - selecting the cgs to a low level , e . g ., 0v . the hv transistor 410 serves as isolation transistor to isolate the negative level into cgs , hence its bulk vcgneg also at a negative level . a circuit 420 , serves as a negative level shifter , is used to provide negative level for cgs . the circuit 420 consists of nand 421 , inverter 422 as enabling entity and hv pmos transistors 423 and 424 and hv nmos transistors 425 and 426 as a cross - coupled negative latch and hv nmos transistor 427 as a buffer . the sources of nmos transistors 425 , 426 , 427 connect to a negative power supply vcgneg . referring to fig7 there is shown third embodiment of a high voltage decoding circuit 420 for positive / negative level signals for use in the memory device 50 of psub cmos process of the present invention . it used a diode decoding scheme for negative voltage . the circuits 310 - 370 are same or similar as those of fig5 . a circuit 510 consisting of hv pmos transistor 512 is used to provide negative level into cgs . the transistor 512 is diode - connected , meaning gate - drain connected together , and its gate - drain is connected to a negative power supply vcgneg . its source is connected to cg . hence as the negative power supply vcgneg goes negative , the source of the transistor goes negative by an amount = vcg neg −| vtp |. referring to fig8 there is shown a negative charge pump 600 that generates the negative voltages that are applied to the coupling gate 26 during the erase operation . a circuit 610 consists of pmos transistors 612 and 613 and capacitors 611 and 614 constitutes a pump stage . the transistor 613 is the transfer transistor ( transferring charge from one stage to next stage ). the transistor 612 and the capacitor 611 serves as vt - cancelling function for the transferring transistor 613 . the capacitor 614 is the pump capacitor ( meaning provide pumping charge ). a diode - connected pmos transistor 620 connects to a power supply node to first pump stage . a diode connected pmos transistor 640 serves to connect to an output charge pump node from last pump stage . pmos transistors 650 and 652 serve to clamp or initialize internal pumped nodes . various clock generation , phase driver , and biases are not shown . referring to fig9 there is shown an embodiment of a negative high voltage regulation circuit 700 for use in the memory device 50 of the present invention . capacitors 702 and 704 are used to divide the negative voltage from the negative power supply vcgneg 399 into a voltage to be compared with a reference voltage vref 708 , e . g . 1v . the vref 708 is coupled to a terminal of a comparator 710 . a transistor 714 is used to initialize node 706 to a bias voltage , e . g ., 2v . the node 706 is coupled to other terminal of the comparator 710 . as the negative supply vcgneg 399 is pumped negative progressively from a level such as ground , the node 706 proportionally goes from a bias level , e . g . positive 2v , to progressively lower in a negative direction ( by the ratio determined by values of the capacitors 702 and 704 ). once the node 706 reaches a value equal to vref 708 , the comparator 710 switches polarity . the output regout 718 is then used to signal that the negative power supply vcgnmeg 399 has reached a desired level such as − 9v used for cg in erase condition . referring to fig1 there is shown an embodiment of a negative test pad circuit 800 for use in the memory device 50 in psub cmos process of the present invention . pmos transistor 810 serves to isolate nmos transistor 812 to a negative level to be transferred from internal to external pad or vice versa . the transistor 810 has its bulk connected to its drain for the purpose of isolation . the transistor 812 serves as esd clamping . referring to fig1 a and 11b there are shown prior art embodiments of a process flow cross section 900 and 901 to produce memory cells having positive high voltage operation of the prior art . a memory cell includes layer 902 ( oxide , sin ), 904 ( cg poly ), 905 ( ono ), 906 ( fg poly ), 908 ( eg poly ), 912 ( sl diffusion layer ), 910 ( oxide between eg and sl ), 914 ( fg gate oxide ), 916 ( side nitride layer ), 955 ( wl poly ). for process flow cross section 900 , peripheral hv device includes 982 ( gate poly ), 988 ( channel region underneath the gate poly ), ldd 980 ( ldd implant ). for this case the peripheral hv gate poly 982 is thick which can stop the ldd implant 980 from going into the channel region 988 . for process flow cross section 901 , which is applicable to advanced smaller geometry technology node , the memory cell includes thin wl poly 965 ( thin compared to the thickness of the wl 955 shown in fig1 a ), and peripheral hv device includes 984 ( gate poly ), 988 ( substrate ), ldd 980 ( ldd implant ). the gate poly 984 is significantly thinner than that of the gate poly 982 . in this case ldd implant 980 penetrates gate poly 984 into the channel region 988 which modulate the channel 988 electrically . this effect is undesirable . in this case additional masking and / or process layer step may be needed to stop ldd implant from penetrating into the channel . referring to fig1 c there is shown an embodiments of a process flow for the production of memory cells 10 having negative voltage operation for use in the memory device 50 in the present invention . ldd implant 981 in this case is significantly lower energy due to the lower high voltage requirement , e . g . 9v vs . 11v for negative voltage operation . hence in this case even with smaller geometry technology node , with thin gate poly 982 thickness , ldd implant does not penetrate into the channel 988 . this process flow hence is suitable for producing memory cell for use with negative voltage operation . the benefits of applying a negative voltage to the word line 22 of the unselected or selected memory cells 10 during the operations of read , erase and program are to allow the memory cell to be scaled down more effectively . during erase , negative voltage on wordline of selected memory cells allows overall erase voltage to be lowered thus allowing cell dimension to be smaller ( sustaining less voltage across various inter - cell or inter - layer dimensional horizontal or vertical spacing , isolation , width , length , etc . . . . ). during program , negative voltage on wordline of unselected memory cells reduces leakage for un - selected memory cells leading to less disturb ( for un - selected cells in same sector ), more accurate programming current ( for selected cells , less leakage interference ) and less power consumption . for read , negative voltage on wordline of unselected memory cells leads to more accurate sensing due to less interference from leakage . it is also advantageous to combine negative wordline , negative coupling gate and negative p substrate for use in memory array operation resulting in lowered erase / program voltages and current , more effective erasing and programming , less cell disturb , and less cell leakage .