the disclosed subject matter will be described next in detail based on the exemplary embodiments shown in the figures . the basic detector circuit of the capacitive type lock switch can be configured as shown in fig1 . in this case , a capacitance 1 is the target capacitance provided , for example , in a door handle , latch , or the like of the vehicle . a converter 2 is a circuit operative to convert a value of the capacitance 1 into a voltage or a digital signal . a high - pass filter 3 is a circuit operative to remove a dc component from an output signal from the converter 2 . a comparator 4 is a circuit operative to binarize an output signal from the high - pass filter 3 . consideration is now given to the case where a human body or the like touches the capacitance 1 to increase the capacitance 1 in fig1 . in this case , an output v 1 from the converter 2 also increases . if the rate of increase in the capacitance 1 is sufficiently higher than a time constant of the high - pass filter 3 , then the output v 1 from the converter 2 , an output v 2 from the high - pass filter 3 , and an output v 3 from the comparator 4 vary as shown in fig2 . in fig2 , vth 1 and vth 2 denote a threshold level for turning the output v 3 from the comparator from low level to high level , and a threshold level for turning it from high level to low level , respectively . in this way , an increase in the capacitance 1 can be detected . as an example of digitally detecting the variation in the capacitance 1 , the converter can be configured as shown in fig3 . in this example , a capacitance 5 determines the oscillation period of a reference oscillator 6 and is made invariable . the capacitance 5 is defined as a reference capacitance . a capacitance 8 determines the oscillation period of an oscillator 9 . the capacitance 8 is defined as a target capacitance . the reference capacitance 5 has a value of c 1 and the reference oscillator 6 has an oscillation period of t 1 . the oscillation period t 1 of the reference oscillator 6 is proportional to the value c 1 of the reference capacitance 5 and can be represented by the following expression . the target capacitance 8 has a value of c 2 and the oscillator 9 has an oscillation period of t 2 . a relation between the oscillation period t 2 of the oscillator 9 and the value c 2 of the target capacitance 5 can also be represented by the following expression that is similar to ( expression 1 ). a counter 7 is considered first . the counter 7 is given an achievable maximum of n 1 and has two outputs . the one output d 1 increases in response to a rising edge of the output from the reference oscillator 6 . the other output v 5 is a one - bit signal that turns high ( h ) when the value of d 2 reaches the achievable maximum n 1 . thus , v 5 provides a pulse with a pulse width of t 1 and a period of ( n 1 × t 1 ). a counter 10 is considered next . the counter 10 counts rising edges of the output v 6 from the oscillator 9 and provides an output v 7 of high ( h ) when the count reaches n 2 or more certain times . the counter 10 is reset when the output v 5 from the counter 7 turns high ( h ). the output v 4 from the reference oscillator , the outputs d 1 and v 5 from the counter 7 , the output v 6 from the oscillator connected to the target capacitance , and the output v 7 from the counter have a relation as shown in fig4 . a falling edge of v 5 , or the reset signal to the counter 10 , and a rising edge of the signal v 6 fed from the oscillator 9 to the counter 10 immediately after that falling edge have a time difference of t 3 therebetween . the output d 1 from the counter 7 at a rising edge of the output v 7 from the counter 10 has a value of n 3 . in this case , the following expression is realized . as the achievable value of t 3 ranges from 0 to t 2 , ( expression 3 ) can be written as follows if n 2 is sufficiently larger than 1 . when t 1 and t 2 in ( expression 4 ) are substituted with ( expression 1 ) and ( expression 2 ), the value n 3 of the output d 1 from the counter 7 at a rising edge of the output from the counter 10 is represented by the following expression . in the data latch 11 of fig3 , the value of input data d 1 is latched in response to a rising edge of v 7 and the latched value is output from d 2 . in this case , the value of n 3 is output from d 2 . consideration is given to the case where the target capacitance c 2 varies from c 3 to c 3 + c 4 . when the target capacitance c 2 is equal to c 3 , d 2 has a value of n 4 and when the target capacitance c 2 is equal to c 3 + c 4 , d 2 has a value of n 5 . in this case , n 4 and n 5 are represented by the following respective expressions . n 4 ={( c 3 × r 2 )/( c 1 × r 1 )}× n 2 ( expression 6 ) n 5 =[{( c 3 + c 4 )× r 2 }/( c 1 × r 1 )]× n 2 ( expression 7 ) from ( expression 6 ) and ( expression 7 ), a variation n 6 in n 3 when the target capacitance c 2 varies from c 3 to c 3 + c 4 is represented by the following expression . n =( n 5 − n 4 )={( c 4 × r 2 )/( c 1 × r 1 )}× n 2 ( expression 8 ) c 1 , r 1 , r 2 and n 2 in ( expression 8 ) are previously given constants . accordingly , measurement of the output d 2 from the data latch 11 allows the variation c 4 in the target capacitance to be derived independent of the initial value c 3 of the target capacitance . in the case of multiple channels , the channels can share the reference capacitance 5 , the reference oscillator 6 and the counter 7 . these operations make it possible to detect a variation in capacitance due to a touch of the human body or the like . in this case , though , a touch regardless of the will of the user may possibly cause the detector to respond . to reduce this possibility , a circuit is added such that the output from the comparator responds only to a touch over a certain time t 4 . a circuit having an arrangement shown in fig5 can be used for that purpose , and is used for the high - pass filter 3 and part of the comparator 4 in fig1 . in fig5 , a difference between an original signal and a signal passed through a low - pass filter 12 is used as the output from the high - pass filter 3 shown in fig1 . in fig5 , an input signal to the low - pass filter 12 is denoted with d 3 and an output signal from the low - pass filter 12 is denoted with d 4 . when the value of the input signal d 3 varies from n 7 to n 8 , the output signal d 4 from the low - pass filter 12 varies from n 7 to n 8 in accordance with a time constant thereof . in this case , subtraction of the signal that has passed through the low - pass filter 12 from the original signal yields a value of ( d 3 − d 4 ). therefore , when the value of the input d 3 to the low - pass filter 12 varies from n 7 to n 8 , the value ( d 3 − d 4 ) from subtraction of the signal passed through the low - pass filter varies from 0 to ( n 8 − n 7 ). thereafter , it gradually approaches 0 in accordance with the time constant of the low - pass filter . the comparator 13 varies the output v 8 from low ( l ) to high ( h ) at a threshold level vth 3 and high to low at a threshold level vth 4 . in this case , when the variation ( n 8 − n 7 ) in the input signal d is higher than vth 3 , the comparator 13 varies the output v 8 from low to high . a timer 14 provides an output v 9 of high when the output v 8 from the comparator 13 is made low . in this state , the timer 14 is kept reset . immediately after the comparator 13 varies the output v 8 from low to high , the output v 9 varies from high to low . when a time t 4 elapses immediately after the output v 9 turns low , the output v 9 turns high again . if the target capacitance returns to the original value when the output is high , that is , the input to the low - pass filter varies from n 8 to n 7 , d 4 takes a value from n 7 to n 8 . therefore , the input ( d 3 − d 4 ) to the comparator 13 has a value within a range between (− n 8 ) and 0 . accordingly , the output v 8 from the comparator 13 becomes low . in this case , the output v 9 from the timer 14 becomes high and the timer 14 is reset . as for the low - pass filter 12 , only when the output v 9 from the timer 14 is high , do clock signals v 9 for use in the low - pass filter 12 become effective . when the output v 9 from the timer 14 is low , the clock signals v 9 are ineffective . while the timer 14 keeps the output v 9 at low for the period of time t 4 , the low - pass filter 12 keeps the output unchanged . when the time t 4 elapses after the input d 3 to the low - pass filter 12 turns high , the low - pass filter 12 starts normal operation . when the output v 8 from the comparator and the output v 9 from the timer are both at high , the final detection signal v 11 exhibits high , which is regarded as an occurrence of the variation in capacitance . a variation in capacitance for a short time less than the time t does not vary the status of a circuit having a data retaining function , or the low - pass filter 12 and the timer 14 . this is equivalent to the case where such variation in capacitance did not arise . with respect to these operations , the states of the signals are as shown in fig6 . the above operations make it possible to realize a circuit operative to respond only to a variation in capacitance over a certain time t 4 . an occurrence of the variation in capacitance over the certain time t 4 increases the output v 8 from the low - pass filter 12 . thereafter , when the target capacitance is not touched , that is , the capacitance returns to the pre - detection value v 7 , the output d 4 from the low - pass filter 12 approaches n 7 in accordance with the time constant thereof . during the process of approach of the output d 4 to n 7 , the value of d 4 is slightly higher than n 7 . therefore , the level of the minus input to the comparator 13 increases to lower the sensitivity . to shorten the time of the lowered sensitivity , a tilt / slope detector circuit 16 can be provided . the output d 4 from the low - pass filter 12 is considered when the input d 3 varies from n 7 to n 8 . if the target capacitance is continuously touched , d 4 varies on a curve having an asymptote to n 8 , with a tilt / slope of 0 or more . thereafter , when the target capacitance is not touched , the tilt / slope of d 4 reaches a value less than 0 . a variation in the tilt / slope is detected at the tilt / slope detector 16 and , if it determines that the tilt / slope is below a certain value , data is set such that the output d 4 from the low - pass filter 12 reaches the value of the input d 3 . the longer the certain time t 4 , the better the erroneous operation can be prevented . in consideration of the general convenience to use , though , 0 . 3 - 1 . 5 seconds may be regarded as a desirable time . fig8 shows a circuit arrangement according to another embodiment of the disclosed subject matter . this circuit includes a counter 1 configured to count reference signals , and a counter 2 configured to count the outputs from the counter 1 . the count in the counter 2 is sequentially stored in a memory at the timing of the output from the counter 1 . a microcomputer can determine when the count varies above a certain level , and provides an on signal when a certain or more variation continues over a set time . fig9 shows a timing chart for the embodiment of fig8 . when the count n 1 , n 2 during non - detection becomes a count lower than a certain level n ( for example , as shown in n 3 , n 4 , n 5 , n 6 ) and the duration continues longer than t 1 , an output signal is generated . while there has been described what are at present considered to be exemplary embodiments of the invention , it will be understood that various modifications may be made thereto , and it is intended that the appended claims cover such modifications as fall within the true spirit and scope of the invention . all conventional art references described above are herein incorporated in their entirety by reference .