with the intention of giving a background to the problems solved by the inventive concept , fig1 illustrates permitted nominal and actual loads directly on a final amplifier in a transmitter . the figure shows a nominal working line where the amplifier is subjected solely to resistive loads . linear transmitter amplifiers are intended for a given nominal load , these amplifiers being able to deliver maximum output power and still remain linear ( this includes feedback couplings and linearising couplings ). in the case of a purely resistive load , the ratio z 0 between voltage ( u ) and current ( i ) is precisely as illustrated by the nominal working line in fig1 . the amplifier functions linearly along this line up to the maximum nominal power that can be outputted . it will be seen that when the impedance of the load on the amplifier becomes low and an attempt is made to adjust to a nominal voltage , the stage will become non - linear and over - modulated . thus , i max will be exceeded . similarly , if an attempt to adjust to i max is made in the case of a high load impedance , u max will be exceeded with subsequent distortion and non - linearity as a result . fig2 illustrates a coupling according to one preferred embodiment of the invention , where a transmitter 11 including at least one amplifying stage receives some form of input signal 10 . this input signal may be any type of signal whatsoever , although , in the case of the illustrated embodiment , it is assumed for the sake of simplicity that the signal is an rf signal that shall be amplified and then transmitted via an antenna / load 12 . the antenna thus functions as load and in this nature is a troublesome antenna since the load it represents and constantly sensed by the transmitter may vary significantly with time , as earlier mentioned . some form of detector circuit may be used to measure voltage and current on the transmitter output signal 13 . as will be seen from fig2 , there is used in this preferred embodiment a double diode detector 14 that has two connection points 15 and 16 between transmitter 11 and load 12 . it will be noted that any standard voltage meter whatsoever may be used to detect the voltage . the diode detector is therefore merely an example of a simple and efficient voltage detector . it is known that the magnitude of a voltage on a transmission line is the same at the transmitter amplifier output as at a point n * 180 degrees closer to the load . this applies to the current , which is also periodic in n * 180 degrees . a point 15 is marked 180 degrees from the output in the figure . this point thus coincides with the first connecting point of the diode detector 14 . since the current is displaced through 90 degrees relative to the voltage at all points along the transmission line , as illustrated in fig3 , the magnitude of the voltage 90 degrees from point 15 , either towards the amplifier or towards the load , corresponds to the current in the amplifier . here illustrated by the second connection point 16 of the diode detector . the two connection points of the diode detector 14 between transmitter 11 and load 12 are therefore positioned so that the distance between said connection points on the transmission line will correspond to +/− n * 90 degrees ( a quarter - wavelength ) along said line so as to obtain two voltages , of which one corresponds to the output voltage and the other corresponds to the output current . one of the measuring points is therefore placed * 180 degrees from the output . the figure shows the position of the detector between amplifier 11 and control circuit 17 . although the voltage could be measured directly on the output ( n = 0 ), it is preferred rather to measure the voltage slightly outwards on the transmission line . this is because the voltage is often easier to measure at a point n * 180 degrees ( n = 1 , 2 , 3 . . . ) from the output . since the current is awkward to measure , it is therefore easier to measure the voltage at a point 16 which is located +/− 90 degrees from point 15 . this point thus represents instant value of the voltage and the current . thus , fig3 illustrates current and voltage between transmitter and load along the entire line between transmitter and load . it will be seen that current and voltage are mutually offset by 90 degrees at each given point between amplifier and load . the coupling illustrated in fig2 therewith gives an output voltage 13 which is determined by whether the voltage or z 0 times the current in the amplifier is greatest at that moment in time , i . e . by which of the magnitudes i and u lie closest to their maximum ( i max or u max ). the greatest of these magnitudes is determined by whether movement is along a load line that corresponds to low or high impedance in accordance with what is shown in fig1 . subsequent to rectification , this output voltage 13 thus constitutes the output signal from the detector 14 and is used as the real value 18 in an amplifier control coupling 17 . there is preferably used as a set - point value 19 a signal that corresponds to the amplitude modulation envelope of the signal at that instance , multiplied by the gain of the amplifier at nominal load , so as to obtain the standard value at which the amplifier shall manage to operate in linear ranges . a comparison is then made and the difference between real value and set - point value results in the signal 20 which is fed back into the transmitter . this signal then regulates the drive power for instance , and therewith the output amplitude of the amplifier . quadrature modulation is one known method of generating linear modulation . two baseband signals each modulate a respective hf signal with respect to amplitude , where said signals are offset by 90 degrees in relation to each other . the modulated signals are summated to obtain a desired signal that is phase - modulated and amplitude - modulated . a typical method of linearising of the amplification chain in a transmitter for quadrature modulation is to use quadrature feedback coupling . an hf signal from the amplifier output is divided by down - mixing with hf signals offset through 90 degrees in quadrature components in the baseband . the quadrature components are then used as real values in amplitude feedback loops for corresponding modulating baseband signals . in order for the present invention to be applied in such a transmitter , the signal to be returned from the transmitter output to the quadrature feedback circuit should represent the voltage or current that is greatest in relation to its nominal value . fig4 illustrates such an arrangement in which a chosen output signal 49 representing current or voltage from the transmitter amplifier chain 50 is fed back to the quadrature circuits 40 . as with the previous embodiment , the connection from the transmitter 50 to the load 51 includes two lead terminals 41 and 42 and a detector circuit 48 , which in a preferred embodiment comprises two diode detectors 43 and 44 that have a common output . one output thus represents voltage on the amplifier output 52 , while the other represents current . in this embodiment , the voltage representing output is referenced 42 and the current representing output is referenced 41 . the detector circuit 48 functions to supply a logic decision circuit 45 which controls a switch 46 to the outlet on the transmitter output that gives the highest detected voltage . the switch 46 thus connects the measuring input of the quadrature feedback - coupling to the line outlet that has the highest amplitude , said detector output signal 49 being used as a real value in the transmitter . the arrangement that includes the switch solves the problem of including the entire signal , which is necessary in respect of quadrature feedback - coupling , and not only the rectified variant which would have been the case if the detector circuit shown in fig2 had been used . the logic decision circuit 45 may be a simple comparison circuit , i . e . a comparator . in order to obtain a decision circuit that functions smoothly , it is also conceivable to provide the diodes with given filtration with respect to amplitude detection . the embodiment shows that the same function as that obtained with the embodiment shown in fig2 can also be achieved with a quadrature feedback - coupled control system . other embodiments in which other parameters are controlled in the feedback coupling are conceivable . for example , an increase in the gain of the amplifier or the attenuation in a variable attenuator . alternatively , it is conceivable to control or regulate a digital / analogue multiplier used in generating the baseband signal earlier in the modulation chain . it will be noted that the aforedescribed invention will also provide advantages in respect of a linear amplifier . a non - linear amplifier also obtains advantages when the danger of over - modulation exists .