exemplary embodiments of the present invention are described in detail referring to the drawings . fig1 is a perspective view schematically illustrating an antenna device according to a first exemplary embodiment of the present invention . referring to fig1 , the antenna device in the exemplary embodiment includes a conductive substrate 1 configured such that dielectric layers ( not illustrated in fig1 ) and conductor layers ( not illustrated in fig1 ) are laminated to each other , a 2 . 4 ghz - band split ring resonator antenna 10 , and a 5 ghz - band split ring resonator antenna 20 that are formed on the conductive substrate 1 . hereinafter , the 2 . 4 ghz - band split ring resonator antenna 10 , and the 5 ghz - band split ring resonator antenna 20 are also respectively abbreviated as an “ sr resonator antenna 10 ” and an “ sr resonator antenna 20 ”. the 2 . 4 ghz - band sr resonator antenna 10 includes an opening 2 a , conductor vias 3 , a feeder line 4 a , and a split portion 5 a . the 5 ghz - band sr resonator antenna 20 includes an opening 2 b , conductor vias 3 , a feeder line 4 b , and a split portion 5 b . the sr resonator antennas 10 and 20 are respectively formed with a conductor layer having a substantially c - shape ( or a c - shape ( hereinafter , the same description is applied .)) in the periphery of the openings 2 a and 2 b in this order . specifically , the conductor layer having a substantially c - shape has a structure such that the portions indicated as the split portions 5 a and 5 b are respectively cut away in this order . the conductor layer having a substantially c - shape is respectively formed as a first split ring portion 31 and a second split ring portion 32 to be described later . the first split ring portion 31 and the second spilt ring portion 32 are disposed so as to overlap each other . in the following description , the openings 2 a and 2 b may be generically called as an “ opening 2 ”. further , the sr resonator antennas 10 and 20 are respectively formed on the conductive substrate 1 in this order in such a manner that the side portions of the sr resonator antennas 10 and 20 where the split portions 5 a and 5 b are formed are exposed on one end surface of the conductive substrate 1 . in the following description , the split portions 5 a and 5 b may be generically called as a “ split portion 5 ”. the conductor vias 3 are schematically illustrated as gray squares in fig1 . specifically , as illustrated in fig4 , each concrete structure of the conductor vias 3 is a cylindrical through - hole , for instance . portions , which are schematically illustrated as white squares adjacent to the conductor vias 3 in a circumferential direction of the opening 2 , represent the conductive substrate 1 . fig4 is a perspective view of another antenna device according to the first exemplary embodiment . the structure of the conductive substrate 1 is described . fig2 is a sectional view of the antenna device taken along the line a - a illustrated in fig1 . as illustrated in fig2 , the conductive substrate 1 includes a plurality of layers configured such that dielectric layers 35 and conductor layers 36 are alternately laminated to each other . in the exemplary embodiment , the conductive substrate 1 includes a dielectric layer 35 and a conductor layer 36 in each of the first layer to fifth layer in one instance . the sixth layer extending along the fifth layer includes only a conductor layer 36 . to simplify the description , the conductor layer 36 including the first layer serving as the outermost surface of the conductive substrate 1 is also called as a first conductor layer 36 a . in the sr resonator antennas 10 and 20 illustrated in fig1 , a first split ring portion 31 a and a first split ring portion 31 b of a substantially c - shape are respectively formed in this order in the first layer constituted of the first conductor layer 36 a and a dielectric layer 35 . in the following description , the first split ring portions 31 a and 31 b may be generically called as a “ first split ring portion 31 ”. as illustrated in fig2 , the second to fifth layers have a structure ( a structural member ) such that a second conductor layer 36 b and a dielectric layer 35 are alternately laminated to each other . the sixth layer is constituted of a first conductor layer . a second split ring portion 32 a and a second split ring portion 32 b having a substantially c - shape , which are not illustrated in fig2 , are formed in each of the second to fifth layers , and the sixth layer . specifically , in the schematic structure diagram illustrated in fig1 , illustration of dielectric layers formed between the layers illustrated in fig2 is omitted . in the following description , the second split ring portions 32 a and 32 b may be generically called as a “ second split ring portion 32 ”. in the exemplary embodiment , description is made based on the premise that the second split ring portion 32 has the second to sixth layers , namely , five layers in total . the number of layers of the antenna device of the present invention as described by the exemplary embodiment for instance , however , is not limited to five . further , the sixth layer is a layer such that a conductor layer 36 constitutes a part of the second split ring portion 32 , and on which the feeder line 4 a and the feeder line 4 b to be described later are provided ( drawn ). in the following description , the feeder lines 4 a and 4 b may be generically called as a “ feeder line 4 ”. the openings 2 a and 2 b illustrated in fig1 are in a state such that the openings are schematically formed solely by the conductor layers 36 because the illustration of the actually existing dielectric layers 35 is omitted to simplify the description . in other words , there is no physical opening that passes through the antenna device in the exemplary embodiment . the configuration of each of the sr resonator antennas 10 and 20 is further described referring to fig1 and fig2 . the 2 . 4 ghz - band sr resonator antenna 10 is provided with the first split ring portion 31 a and the second split ring portion 32 a which overlap each other ( fig1 ). the split portion 5 a is a clearance formed by cutting away the 2 . 4 ghz - band sr resonator antenna 10 at a position of the opening 2 a . the split portion 5 a is constituted of a first split portion 51 a corresponding to the first layer , and a second split portion 52 a corresponding to the second to sixth layers . in other words , the first split ring portion 31 a and the second split ring portion 32 a are respectively formed to surround the opening 2 a in a cutaway state as illustrated by the first split portion 51 a and the second split portion 52 a in fig1 . the first split ring portion 31 a and the second split ring portion 32 a have a structure such that the first layer and the second to sixth layers are laminated to each other . the 5 ghz - band sr resonator antenna 20 has substantially the same structure as the 2 . 4 ghz - band sr resonator antenna 10 . specifically , the 5 ghz - band sr resonator antenna 20 is provided such that the first split ring portion 31 b and the second split ring portion 32 b overlap each other ( fig1 ). the split portion 5 b is a clearance formed by cutting away the 5 ghz - band sr resonator antenna 20 at a position of the opening 2 b . the split portion 5 b is constituted of a first split portion 51 b corresponding to the first layer , and a second split portion 52 b corresponding to the second to sixth layers . specifically , the first split ring portion 31 b and the second split ring portion 32 b are respectively formed to surround the opening 2 b in a cutaway state as illustrated by the first split portion 51 b and the second split portion 52 b in fig1 . the first split ring portion 31 b and the second split ring portion 32 b have a structure such that the first layer and the second to sixth layers are laminated to each other . in the sr resonator antennas 10 and 20 , the first split portions 51 a and 51 b are respectively and generically called as a first split portion 51 . further , in the sr resonator antennas 10 and 20 , the second split portions 52 a and 52 b are respectively and generically called as a second split portion 52 . the 2 . 4 - ghz band sr resonator antenna 10 is called as a first split ring resonator antenna 10 which resonates at a first frequency i . e . a frequency in 2 . 4 ghz band . the 5 - ghz band sr resonator antenna 20 is called as a second spilt ring resonator antenna 20 which resonates at a second frequency i . e . a frequency in 5 ghz band . specifically , the antenna device in the exemplary embodiment is a structural member configured such that the dielectric layers 35 and conductor layers are alternately laminated to each other . the antenna device includes the first split ring portion 31 , which is formed in the first conductor layer 36 a extending on one surface side of the dielectric layer 35 , which surrounds the opening 2 , and which includes the first split portion 51 formed in a part of the circumferential direction along the opening 2 . the antenna device includes the second split ring portion 32 , which is formed in the second conductor layer 36 b extending on the other surface side of the dielectric layer 35 , which surrounds the opening 2 formed to face the first split ring portion 31 , and which includes the second split portion 52 formed in a part of the circumferential direction along the opening 2 . the antenna device includes a plurality of the conductor vias 3 which are formed to be away from each other at an interval circumferentially while sandwiching the first split portion 51 and the second split portion 52 for electrically connecting the first split ring portion 31 and the second split ring portion 32 . the antenna device includes the feeder line 4 , which is formed on a specific one of the conductor layers , with one end thereof electrically connected to at least one of the conductor vias 3 , and the other end thereof insulated from the specific conductor layer via a clearance 39 formed in the specific conductor layer along an extending direction of the specific conductor layer . the antenna device in the exemplary embodiment has a plurality of the aforementioned structures , wherein the first one of the structures constitutes the first split ring resonator antenna 10 which resonates at the first frequency , and the second one of the structures constitutes the second split ring resonator antenna 20 which resonates at the second frequency . the antenna device in the exemplary embodiment includes the first split ring resonator antenna 10 which is provided with the aforementioned constituent elements and resonates at the first frequency , and the second split ring resonator antenna 20 which is provided with the aforementioned constituent elements and resonates at the second frequency . the conductor vias 3 are conductive members which are formed to be away from each other at a predetermined interval so as to surround the opening 2 for electrically connecting the conductor layers 36 of the first to sixth layers of the conductive substrate 1 , and a feeding point 6 to be described later . the predetermined interval at which the conductor vias 3 are formed is e . g . 1 mm ( millimeter ). however , the interval between the conductor vias 3 is not limited to 1 mm . one end of the feeder line 4 a and one end of the feeder line 4 b are respectively connected in this order to unillustrated wireless units ( high - frequency circuits ) of 2 . 4 ghz band and of 5 ghz band . the other end of the feeder line 4 a and the other end of the feeder line 4 b are respectively connected in this order to a feeding point 6 a and to a feeding point 6 b ( hereinafter , also generically called as a “ feeding point 6 ”) of the sr resonator antennas 10 and 20 for supplying and receiving high - frequency current to and from the wireless units of the respective frequency bands . for instance , the feeder line 4 of the sixth layer and another conductor layer 36 are electrically connected to each other via at least one of the conductor vias 3 at the feeding point 6 . it is assumed that the feeder line 4 has , for instance , a rectangular conductive pattern in a cross - section perpendicular to the length direction of the feeder line 4 , so that impedance matching with an input and output port of the wireless unit is considered . a clearance is formed around the feeder lines 4 a and 4 b so that the feeder lines 4 a and 4 b are not short - circuited to the conductor layers 36 around the feeder lines 4 a and 4 b when the feeder lines 4 a and 4 b are connected to the respective wireless units . the clearance 39 is set to 0 . 5 mm , for instance . however , the clearance 39 to be formed around the feeder line 4 is not limited to 0 . 5 mm . in the foregoing description , the feeder line 4 is drawn from the sixth layer of the second split ring portion 32 illustrated in fig2 , in one instance . however , the method for drawing the feeder line 4 is not limited to the aforementioned method . for instance , it is possible to draw the feeder line 4 from the conductor layer 36 ( namely , from the first conductor layer 36 a ) on the outermost surface ( the first layer ) of the first split ring portion 31 . as illustrated in fig4 , the feeder line 4 may be formed and drawn , using the conductor layer 36 in at least one of the inner layers ( namely , one of the second to fifth layers ) in the second split ring portion 32 . fig4 is a perspective view of another antenna device in the first exemplary embodiment . to simplify the description , in fig4 , the 2 . 4 ghz - band sr resonator antenna 10 formed on the conductive substrate 1 is simply illustrated as a conductor layer on which a split ring portion 12 a and the feeder line 4 a are formed . therefore , in fig4 , illustration of the dielectric layers and the 5 ghz - band sr resonator antenna 20 is omitted . in the sr resonator antennas 10 and 20 illustrated in fig1 , the layers from which the feeder line 4 is drawn may be different from each other . the material of the conductor layers 36 constituting a part of the conductive substrate 1 illustrated in fig1 includes , for instance , a conductive metal pattern such as a copper film pattern . the material of the dielectric layers 35 constituting a part of the conductive substrate 1 illustrated in fig1 is , for instance , a glass epoxy substrate for use in a printed substrate . however , the material of the dielectric layers 35 is not limited to the above , but may be a ceramic substrate or the like . next , structures of the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 , which are respectively configured to resonate at a frequency in 2 . 4 ghz band and at a frequency in 5 ghz band in this order , are described . the sr resonator antennas 10 and 20 respectively resonate in the aforementioned frequency bands by the length of the conductive members surrounding the outer periphery of the respective openings 2 , and by the electrostatic capacitance between counter electrodes 7 sandwiching the split portion 5 , which will be described later . the sr resonator antennas 10 and 20 respectively include counter electrodes 7 a and 7 b facing each other ( making pairs ), which are formed at a right angle on the split portions 5 a and 5 b while extending from the opening end of the split portion 5 a and from the opening end of the split portion 5 b toward the opening 2 . hereinafter , the “ counter electrodes 7 a ” and the “ counter electrodes 7 b ” are also generically called as “ counter electrodes 7 ”. the counter electrodes 7 are provided to obtain an electrostatic capacitance c in the spilt portions 5 a and 5 b . specifically , the electrostatic capacitance c is obtained based on the following well - known equation , assuming that s is a total area of the surfaces of the conductor layers 36 facing each other and constituting the counter electrodes 7 sandwiching the split portion 5 , d is a distance between the counter electrodes 7 , and e is a permittivity of the gap between the counter electrodes 7 . as described above , the area s is of the surfaces of the conductor layers 36 facing each other while sandwiching the split portion 5 , and constituting the counter electrodes 7 of each of the antennas . the area s is a product of the sum of thicknesses ( heights ) of the conductor layers 36 , and the length of the counter electrodes 7 which are formed at a right angle while extending from the opening end of the split portion 5 toward the opening 2 . in this example , the electrostatic capacitance between the conductor layers 36 of different layers in the counter electrodes 7 is negligibly small , as compared with the electrostatic capacitance between the conductor layers 36 of the same layers facing each other while sandwiching the split portion 5 . the sum of the heights of the conductor layers of the counter electrodes 7 is , for instance , 0 . 8 mm when the conductor layers are six layers in total . further , the lengths of the counter electrodes 7 of the sr resonator antennas 10 and 20 are respectively 3 . 5 mm and 2 . 5 mm in this order , for instance . however , the aforementioned sizes are merely an example and the present invention is not limited to the aforementioned sizes . the number of the conductor layers 36 constituting the counter electrodes 7 sandwiching the split portion 5 of each of the antennas is not limited to six , but may be any other number , as far as it is possible to obtain a predetermined electrostatic capacitance between the counter electrodes 7 . in the exemplary embodiment , as illustrated in fig1 , the 2 . 4 ghz - band sr resonator antenna 10 includes the conductor layers 36 constituting the counter electrodes in all the six layers in one instance . on the other hand , the 5 ghz - band sr resonator antenna 20 includes , for instance , the conductor layers 36 formed only on the first layer and the sixth layer , and counter electrodes are not formed on the conductor layers other than the above . in other words , forming the conductor layer 36 constituting the counter electrodes 7 of each of the antennas by two or more layers makes it possible to obtain a combined electrostatic capacitance such that the electrostatic capacitances between the counter electrodes of each of the conductor layers 36 are connected in parallel . according to the exemplary embodiment , it is possible to adjust the electrostatic capacitance by the number of the conductor layers 36 constituting the counter electrodes 7 . in the exemplary embodiment , the conductor vias 3 for electrically connecting between the conductor layers 36 are formed only at the feeding point 6 with respect to the counter electrodes 7 sandwiching the split portion 5 in one instance . however , the conductor vias 3 may be formed as necessary with respect to the counter electrodes 7 sandwiching the split portion 5 . the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 respectively resonate at a frequency f in 2 . 4 ghz band and at a frequency f in 5 ghz band in this order , based on the following well - known equation , assuming that c is an electrostatic capacitance between the counter electrodes 7 as described above , and l is an inductive reactance . the inductive reactance l is an impedance given by the line length , which is the length of the conductive members of the conductor layers 36 surrounding the outer periphery of the opening 2 . the electrostatic capacitance c is also called as a “ capacitive reactance ” in the following description . when it is intended to reduce the size of the sr resonator antenna , the line length i . e . the length of the conductive members surrounding the outer periphery of the opening 2 , which serves as the inductive reactance l , is shortened . however , it is necessary to fix the resonance frequency f in the aforementioned target frequency band . therefore , it is necessary to increase the capacitive reactance c between the counter electrodes 7 by using eq . 2 . it is possible to increase the capacitive reactance c between the counter electrodes 7 by the following methods a ) to c ), using eq . 1 . for instance , a ) the total area s of the surfaces of the conductor layers 36 facing each other and constituting the counter electrodes 7 is increased by increasing the length of the counter electrodes 7 . b ) the distance ( gap ) d between the counter electrodes 7 is shortened . c ) the number of the conductor layers 36 constituting the counter electrodes 7 is increased . using one of the aforementioned methods a ) to c ), or combining at least two of the aforementioned methods a ) to c ) makes it possible to increase the capacitive reactance c in the sr resonator antennas 10 and 20 according to the exemplary embodiment . it is also possible to adjust the capacitive reactance c by the thickness ( height ) of the conductor layer 36 , in addition to the aforementioned parameters , as expressed in eq . 1 . further , π in eq . 2 is the circular constant . the size of the antenna device provided with the sr resonator antennas 10 and 20 is described using the drawings . fig3 is a dimensional diagram of the antenna device according to the first exemplary embodiment . referring to fig3 , the length of the side of the 2 . 4 ghz - band sr resonator antenna 10 where the split portion 5 is formed is e . g . 13 mm , and the length of the side of the 5 ghz - band sr resonator antenna 20 where the split portion 5 is formed is e . g . 5 mm . the depthwise length of each of the sr resonator antennas 10 and 20 from the end surface where the split portion 5 is formed to the opening 2 is e . g . 4 . 5 mm . the distance between the two sr resonator antennas is e . g . 4 mm . the unillustrated length ( thickness ) of the conductive substrate 1 in the thickness direction thereof depends on the number of layers of the conductive substrate 1 . the thickness of the conductive substrate 1 is e . g . 1 . 6 mm . the dimensions described using fig3 are merely an example for describing the exemplary embodiment . the present invention is not limited to the dimensions . the sr resonator antennas 10 and 20 are designed such that the sr resonator antennas 10 and 20 resonate at the respective resonance frequencies , independently of each other . the positional relationship between the two sr resonator antennas 10 and 20 may be set such that the positions of the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 are respectively interchanged on left and right sides as illustrated in fig1 . specifically , it is adoptable to interchange the positions of the feeder line 4 a and the split portion 5 a of the 2 . 4 ghz - band sr resonator antenna 10 , and the positions of the feeder line 4 b and the split portion 5 b of the 5 ghz - band sr resonator antenna 20 . the exemplary embodiment is not limited to the sr resonator antenna having the aforementioned shape . as far as it is possible to configure an sr resonator , the sr resonator may have any shape other than the above . the exemplary embodiment is advantageous in implementing an antenna device incorporated with split ring resonators , using a laminated printed substrate . a second exemplary embodiment on the basis of the first exemplary embodiment is described referring to fig5 a to fig1 . in the second exemplary embodiment , a method for designing an antenna device applying the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 according to the first exemplary embodiment is described . in the exemplary embodiment , there is provided a method for adjusting the characteristics of one of the sr resonator antennas for improvement of the characteristics while miniaturizing the antennas when the sr resonator antennas are disposed in proximity to each other . fig5 a and fig5 b , and fig6 a and fig6 b are diagrams respectively illustrating the antenna performances of the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 as individual antennas in this order . fig5 a is a diagram illustrating impedance characteristics of the 2 . 4 ghz - band sr resonator antenna 10 according to the second exemplary embodiment . fig5 b is a diagram illustrating reflection characteristics of the 2 . 4 ghz - band sr resonator antenna 10 according to the second exemplary embodiment . fig6 a is a diagram illustrating impedance characteristics of the 5 ghz - band sr resonator antenna 20 according to the second exemplary embodiment . fig6 b is a diagram illustrating reflection characteristics of the 5 ghz - band sr resonator antenna 20 according to the second exemplary embodiment . the impedance characteristics represent impedances ( a real part and an imaginary part of impedance characteristics ) of each of the sr resonator antennas 10 and 20 . specifically , the horizontal axis ( a horizontal line ) of the circle illustrated in fig5 a and fig6 a represents a net resistance ( a real part of impedance characteristics ) of each of the sr resonator antennas 10 and 20 . the center point of the horizontal line represents 1 , which is a numerical value normalized by 50ω . the left end of the horizontal line represents 0ω ( namely , a short - circuited state ) and the right end of the horizontal line represents ∞ ( infinite ), ω ( namely , an open state ), on the basis of assuming that the center point of the horizontal line has the numerical value 1 . the line ( an arc ) perpendicularly intersecting with the horizontal line representing a real part represents an imaginary part ( a reactance component ). the impedance characteristics of the sr resonator antenna are expressed in the upper semicircular portion of the circle with respect to the horizontal line in the following case , on the basis of assuming that the center point has the numerical value 1 . specifically , in this case , for instance , an inductive reactance component as illustrated by a line pattern of the split ring portions 31 and 32 is imparted to the sr resonator antenna in series . on the other hand , impedance characteristics of the sr resonator antenna are expressed in the lower semicircular portion of the circle with respect to the horizontal line in the following case , on the basis of assuming that the center point has the numerical value 1 . specifically , in this case , for instance , a capacitive reactance component between the counter electrodes 7 sandwiching the split portion 5 is imparted to the sr resonator antenna in series . the indication 2000 ( 1 . 95 , 51 ) ohm ( ω ) with the white dot in the upper left portion of fig5 a is read as follows . the first numerical value represents a value of frequency , and the numerical values in the bracket respectively represent in this order a value of a real part and a value of an imaginary part of impedance characteristics at the value of frequency with a comma between the values . in other words , the value of the real part of impedance characteristics is 1 . 95ω , and the value of the imaginary part of impedance characteristics is 51ω when the frequency is 2 ghz . specifically , the indication “ frequency / mhz ” in fig5 a represents that the unit of frequency is megahertz . further , the point indicated with the solid dot in the upper left portion of fig5 a represents numerical values of impedance characteristics at 6000 mhz ( 6 ghz ). further , regarding the frequencies described in items 1 to 7 in the lower left portion of fig5 a , the frequencies described in items 1 to 3 respectively represent numerical values of impedance characteristics when the frequency is in 2 . 4 ghz band . further , the frequencies described in items 4 to 7 respectively represent numerical values of impedance characteristics when the frequency is in 5 ghz band . the reading regarding fig5 a as described above is also applied to fig6 a and fig1 a . specifically , impedance characteristics of the 2 . 4 ghz - band sr resonator antenna 10 illustrated in fig5 a , and impedance characteristics of the 5 ghz - band sr resonator antenna 20 illustrated in fig6 a satisfy the impedance characteristics in the respective frequency bands . more specifically , in fig5 a , a reactance component in the vicinity of the center frequency of 2 . 4 ghz band is present in the vicinity of the numerical value 1 representing the center point . likewise , in fig6 a , a reactance component in the vicinity of the center frequency of 5 ghz band is present in the vicinity of the numerical value 1 representing the center point . further , reflection characteristics illustrated in fig5 b and fig6 b respectively represent ratios to be obtained when signals respectively input from the feeder line 4 of the sr resonator antennas 10 and 20 are respectively reflected on the antennas , and the reflected signals return to the feeder line 4 . reflection characteristics are such that the horizontal axis represents a frequency , and the vertical axis represents a ratio of output ( reflection ) power with respect to input power in the unit of db ( decibel ). the horizontal axis representing a frequency in fig5 b and fig6 b is such that the frequency is increased toward the right direction , and the vertical axis representing a reflectance is such that the reflectance is reduced toward the lower direction at the frequency ( in other words , a radio wave is efficiently radiated ). the reflection characteristics of the 2 . 4 ghz - band sr resonator antenna 10 illustrated in fig5 b , and the reflection characteristics of the 5 ghz - band sr resonator antenna 20 illustrated in fig6 b represent that the reflection characteristics in the respective frequency bands are satisfied . specifically , in fig5 b , reflection in the vicinity of the center frequency of 2 . 4 ghz band is reduced . further , in fig6 b , reflection in the vicinity of the center frequency of 5 ghz band is reduced . however , the ratio of reflection ( a return loss value ) at a frequency in 5 ghz band , which is not 2 . 4 ghz - band that is the center frequency of the 2 . 4 ghz - band sr resonator antenna 10 illustrated in fig5 b , is about − 7 db as a smallest value . in other words , the 2 . 4 ghz - band sr resonator antenna 10 has characteristics such that an input signal may be radiated ( leak ) even at a frequency in 5 ghz band , which is a frequency in a frequency band other than 2 . 4 ghz band , as a target frequency . the fact that the 2 . 4 ghz - band sr resonator antenna 10 has characteristics such that a signal may be radiated even at a frequency in 5 ghz band means that the 2 . 4 ghz - band sr resonator antenna 10 is likely to receive a signal of a frequency in 5 ghz band . it is impossible to secure isolation characteristics to be described later using fig7 between the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 , which are disposed in proximity to each other . fig7 is a diagram illustrating isolation characteristics representing a ratio of output power with respect to input power of a signal to be output from the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 when a signal is input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 in the second exemplary embodiment . isolation characteristics are characteristics representing a degree of isolation of a signal between input and output ports different from each other . specifically , in fig3 , the characteristics represent a ratio , in the unit of db , of output power of the feeder line 4 b with respect to input power of the feeder line 4 a when a signal of a frequency , for instance , from 2 ghz to 6 ghz is input to the feeder line 4 a while changing the frequency , and a signal of the frequency is output to the feeder line 4 b . in fig7 , the horizontal axis represents a frequency , and the vertical axis represents an isolation ( a degree of isolation ). the horizontal axis representing a frequency is such that the frequency is increased toward the right direction . the vertical axis representing an isolation is such that leakage of a signal of the frequency to the other sr resonator antenna is reduced toward the lower direction ( namely , the signal is isolated ). referring to fig7 , the ratio of output power with respect to input power of a signal input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 , when the signal leaks to the 5 ghz - band sr resonator antenna 20 and is output from the feeder line 4 b at a frequency in 5 ghz band , is about − 11 db as a largest value . in other words , a signal of a frequency in 5 ghz band that is input to the feeder line 4 a is output from the feeder line 4 b only with attenuation of about 11 db . the sr resonator antennas 10 and 20 have reversibility such that radiation characteristics in transmitting a radio wave become receiving characteristics in receiving a radio wave , as well as another antenna . thus , the power of a signal of a frequency in 5 ghz band that is input to the feeder line 4 b is output from the feeder line 4 a only with attenuation of about 11 db . therefore , the 2 . 4 ghz - band sr resonator antenna 10 also receives a signal of a frequency in 5 ghz band that is radiated from the 5 ghz - band sr resonator antenna 20 , whereby a high - frequency receiving circuit of a wireless unit ( not illustrated ) of 2 . 4 ghz band is saturated . as a result , the wireless unit ( not illustrated ) of 2 . 4 ghz band is incapable of receiving a signal that should be received originally . however , by setting the reflectance ( a return loss value ) at a frequency in 5 ghz band to zero with respect to the impedance characteristics of the 2 . 4 ghz - band sr resonator antenna 10 illustrated in fig5 b , the 2 . 4 ghz - band sr resonator antenna 10 is inoperative as an antenna for receiving a frequency in 5 ghz band . as a result , the high - frequency receiving circuit of the wireless unit of 2 . 4 ghz band is not saturated by the signal of a frequency in 5 ghz band that is radiated from the 5 ghz - band sr resonator antenna 20 ( in other words , the isolation characteristics are improved ). thus , the wireless unit of 2 . 4 ghz band is capable of receiving a signal that should be received originally by the wireless unit of 2 . 4 ghz band . next , an antenna designing method for improving the isolation characteristics is described . isolation characteristics of an electronic device including the aforementioned antenna device at a frequency in 5 ghz band depend on design of a high - frequency circuit including a filter circuit in each of the wireless units and the like . it is assumed that it is necessary to secure e . g . 20 db as the value of isolation characteristics representing a degree of isolation from the 2 . 4 ghz - band sr resonator antenna 10 to the 5 ghz - band sr resonator antenna 20 . in that case , it is necessary to improve the value of isolation characteristics from the current value of about 11 db further by 9 db . it is necessary to increase , for instance , the distance between the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 in order to improve the isolation characteristics by 9 db , without adding a component such as a filter circuit to the high - frequency circuit of the wireless unit . as an example of a simulation result by a computer , as illustrated in fig8 to be described later , it is necessary to secure a distance of e . g . 24 mm between antennas , which is further away 20 mm with respect to 4 mm illustrated in fig3 . the aforementioned distance is a distance when a signal of a frequency in 5 ghz band which may leak from the 2 . 4 ghz - band sr resonator antenna 10 reaches the 5 ghz - band sr resonator antenna 20 by attenuation of 9 db due to transmission loss . fig8 is a dimensional diagram of the shapes and the positions of antennas based on the simulation result . fig8 is a diagram illustrating a distance between antennas when the intensity of a signal of a frequency in 5 ghz band that is radiated from the 2 . 4 ghz - band sr resonator antenna 10 and leaks to the 5 ghz - band sr resonator antenna 20 is reduced by increasing the distance between the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 according to the second exemplary embodiment . according to this configuration , the ratio of output power from the feeder line 4 b with respect to input power of a signal of a frequency in 5 ghz band that is input from the feeder line 4 a satisfies the target value of isolation characteristics i . e . 20 db . however , as illustrated in fig8 , when the distance between the antennas is increased , the size of the conductive substrate 1 on which the sr resonator antennas 10 and 20 are mounted may increase , which may increase the size of the entirety of the antenna device for housing the conductive substrate 1 . in the exemplary embodiment , the shape of the 5 ghz - band sr resonator antenna 20 remains unchanged , and the shape and the position of the 2 . 4 ghz - band sr resonator antenna 10 side are changed when a return loss value of the 2 . 4 ghz - band sr resonator antenna 10 at a frequency in 5 ghz band is improved . further , in the exemplary embodiment , even when the 2 . 4 ghz - band sr resonator antenna 10 and the 5 ghz - band sr resonator antenna 20 are disposed in proximity to each other , the shape and the position of the sr resonator antenna 10 are adjusted to satisfy the predetermined impedance characteristics and the predetermined reflection characteristics of each of the sr resonator antennas 10 and 20 . fig9 is a dimensional diagram of a result when the shape and the position of the 2 . 4 ghz - band sr resonator antenna 10 are changed . further , fig1 a and fig1 b illustrate impedance characteristics and reflection characteristics of the 2 . 4 ghz - band sr resonator antenna 10 in a state that the shape and the position of the 2 . 4 ghz - band sr resonator antenna 10 are changed . fig9 is a diagram , in which the size of the 2 . 4 ghz - band sr resonator antenna 10 is reduced by adjusting the line length of the 2 . 4 ghz - band sr resonator antenna 10 and the counter electrodes 7 sandwiching the split portion 5 according to the second exemplary embodiment . fig9 is also a diagram describing a state that leakage of a signal of a frequency in 5 ghz band is reduced and the distance between the 2 . 4 ghz - band sr resonator antenna and the 5 ghz - band sr resonator antenna is shortened . fig1 a is a diagram illustrating impedance characteristics of the 2 . 4 ghz - band sr resonator antenna 10 when the size of the 2 . 4 ghz - band sr resonator antenna 10 is reduced by adjusting the line length of the 2 . 4 ghz - band sr resonator antenna 10 and the counter electrodes 7 sandwiching the split portion 5 according to the second exemplary embodiment . fig1 a is also a diagram illustrating impedance characteristics of the 2 . 4 ghz - band sr resonator antenna 10 when leakage of a signal of a frequency in 5 ghz band is reduced and the distance between the 2 . 4 ghz - band sr resonator antenna and the 5 ghz - band sr resonator antenna is shortened . fig1 b is a diagram illustrating reflection characteristics of the 2 . 4 ghz - band sr resonator antenna 10 when the size of the 2 . 4 ghz - band sr resonator antenna 10 is reduced by adjusting the line length of the 2 . 4 ghz - band sr resonator antenna 10 and the counter electrodes 7 sandwiching the split portion 5 according to the second exemplary embodiment . fig1 b is also a diagram illustrating reflection characteristics of the 2 . 4 ghz - band sr resonator antenna 10 when leakage of a signal of a frequency in 5 ghz band is reduced and the distance between the 2 . 4 ghz - band sr resonator antenna and the 5 ghz - band sr resonator antenna is shortened . in the exemplary embodiment , the size of the 2 . 4 ghz - band sr resonator antenna 10 is reduced to such an extent that the ratio of reflection power with respect to input power , which represents reflection characteristics at a frequency in 5 ghz band is approximated to zero in the 2 . 4 ghz - band sr resonator antenna 10 . the method for shortening the line length of the 2 . 4 ghz - band sr resonator antenna 10 with respect to the opening 2 a , and increasing the electrostatic capacitance between the counter electrodes 7 sandwiching the split portion 5 is performed based on eq . 1 and eq . 2 , which are described in the first exemplary embodiment . specifically , the antenna device designing method according to the exemplary embodiment is based on the premise that there is reflection power with respect to input power at a frequency in 5 ghz band in the 2 . 4 ghz - band sr resonator antenna 10 . in this case , the line length , which is the length of the conductive members surrounding the outer periphery of the opening 2 a serving as the inductive reactance l component in the 2 . 4 ghz - band sr resonator antenna 10 is shortened . according to the antenna device designing method of the exemplary embodiment , it is possible to increase the electrostatic capacitance ( namely , the capacitive reactance c ) between the counter electrodes 7 in the 2 . 4 ghz - band sr resonator antenna 10 by using eq . 2 , while continuing to use the resonance frequency f as the center frequency of 2 . 4 ghz band . it is possible to increase the capacitive reactance c by the following methods using eq . 1 . specifically , a ) the total area s of the surfaces of the conductor layers 36 facing each other and constituting the counter electrodes 7 is increased by increasing the length of the counter electrodes 7 in the 2 . 4 ghz - band sr resonator antenna 10 . b ) the gap distance d between the counter electrodes 7 is shortened . c ) the number of the conductor layers 36 constituting the counter electrodes 7 is increased . using one of the aforementioned methods a ) to c ), or combining at least two of the aforementioned methods a ) to c ) makes it possible to increase the capacitive reactance c . it is also possible to adjust the capacitive reactance c by the thickness ( height ) of the conductor layer 36 , in addition to the aforementioned parameters . in this section , comparison is made between fig5 a and fig5 b illustrating antenna characteristics of the 2 . 4 ghz - band sr resonator antenna 10 before the size of the 2 . 4 ghz - band sr resonator antenna 10 is adjusted , and fig1 a and fig1 b illustrating antenna characteristics after the size of the 2 . 4 ghz - band sr resonator antenna 10 is adjusted . in this case , it is clear that a return loss value at a frequency in 5 ghz band is improved from about − 7 db to 0 db in the antenna device designing method of the exemplary embodiment . according to this configuration , a signal of a frequency in 5 ghz band that is input to the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 is reflected to the feeder line 4 a . therefore , the 2 . 4 ghz - band sr resonator antenna 10 is not operated as a 5 ghz - band sr resonator antenna ( does not radiate a radio wave ). this means that the signal does not leak to the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 . conversely , a signal of a frequency in 5 ghz band that is input from the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 does not leak to the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 . as illustrated in fig9 , the 2 . 4 ghz - band sr resonator antenna 10 is configured such that the length of the side where the split portion 5 a is formed , and the length of the side opposing to the aforementioned side are shortened from 13 mm illustrated in fig3 to 9 mm illustrated in fig9 . fig1 illustrates isolation characteristics of the sr resonator antennas 10 and 20 illustrated in fig9 . fig1 is a diagram illustrating isolation characteristics when leakage of a signal of a frequency in 5 ghz band is reduced by adjusting the line length of the 2 . 4 ghz - band sr resonator antenna 10 and the counter electrodes 7 sandwiching the split portion 5 according to the second exemplary embodiment . fig1 is also a diagram illustrating isolation characteristics representing a ratio of output power with respect to input power of a signal output from the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 when a signal is input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 in shortening the distance between the 2 . 4 ghz - band sr resonator antenna and the 5 ghz - band sr resonator antenna . referring to fig1 , a return loss of the 2 . 4 ghz - band sr resonator antenna 10 is improved . thus , as illustrated in fig9 , it is clear that it is possible to secure isolation characteristics even when the distance between the sr resonator antennas 10 and 20 is as small as 4 mm , as illustrated in fig3 . specifically , in fig1 , a signal of a frequency in 5 ghz band from the 2 . 4 ghz - band sr resonator antenna 10 to the 5 ghz - band sr resonator antenna 20 is reduced by 20 db or more . the exemplary embodiment is advantageous in reducing leakage of a signal from the sr resonator antenna which resonates in a higher frequency band to the sr resonator antenna which resonates in a lower frequency band . this advantage is implementable without adding a component and the like , even when the split ring resonator antennas for different frequency bands are disposed in proximity to each other . the reason is that reflection characteristics ( a return loss value ) of a higher frequency component of a lower frequency band antenna that is affected by a higher frequency band antenna , are adjusted to approximate to zero when the two split ring resonator antennas are disposed in proximity to each other . further , miniaturizing the lower frequency band antenna configuration , and shortening the distance between the lower frequency band antenna and the higher frequency band antenna is advantageous in miniaturizing an electronic device a third exemplary embodiment on the basis of the first and second exemplary embodiments is described using fig1 a , fig1 b , and fig1 . the exemplary embodiment is different from the first and second exemplary embodiments in a point that the positions of the feeder line 4 b and the split portion 5 b of the 5 ghz - band sr resonator antennas 20 in the first and second exemplary embodiments are interchanged . in the following , the features of the exemplary embodiment are mainly described . the same constituent elements in the exemplary embodiment as the constituent elements in the first and second exemplary embodiments are indicated with the same reference signs , and repeated description of the constituent elements is omitted . in the diagram of fig1 illustrating improved isolation characteristics of the 2 . 4 ghz - band sr resonator antenna 10 at a frequency in 5 ghz band according to the second exemplary embodiment , the isolation characteristics in 2 . 4 ghz band is about − 17 db . therefore , in the example illustrated in fig1 , isolation characteristics are insufficient by about 3 db with respect to the target isolation characteristics i . e . − 20 db . in view of the above , in the exemplary embodiment , as illustrated in fig1 b , the positions of the feeder line 4 b and the split portion 5 b of the 5 ghz - band sr resonator antenna 20 are interchanged from the configuration illustrated in fig9 ( or fig1 a ). fig1 a is a diagram schematically illustrating a flow of high - frequency current i . e . a signal in 2 . 4 ghz band which may leak from the 2 . 4 ghz - band sr resonator antenna 10 before the positions of the split portion 5 b and the feeder line 4 b are interchanged in the 5 ghz - band sr resonator antenna 20 according to the third exemplary embodiment of the present invention . fig1 b is a diagram schematically illustrating a flow of high - frequency current i . e . a signal in 2 . 4 ghz band which may leak from the 2 . 4 ghz - band sr resonator antenna 10 after the positions of the split portion 5 b and the feeder line 4 b are interchanged in the 5 ghz - band sr resonator antenna 20 according to the third exemplary embodiment . this is a configuration for improving isolation characteristics of the 2 . 4 ghz - band sr resonator antenna 10 for the 5 ghz - band sr resonator antenna in the exemplary embodiment . fig1 a illustrates a case , in which the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 is near the position where the 2 . 4 ghz - band sr resonator antenna 10 is disposed . in this case , a signal of a frequency in 2 . 4 ghz band that is input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 slightly leak to the feeder line 4 b of the 5 ghz - band sr resonator antenna along the route indicated by the dotted - line arrow . this is because the impedance of the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 matches with a high - frequency circuit of an unillustrated wireless unit of 5 ghz band to be connected to the feeder line 4 b , and high - frequency current flows from the 2 . 4 ghz - band sr resonator antenna 10 to the feeder line 4 b . as a result , the 5 ghz - band sr resonator antenna 20 also receives a signal of a frequency in 2 . 4 ghz band that is radiated from the 2 . 4 ghz - band sr resonator antenna 10 , whereby the high - frequency receiving circuit of the wireless unit of 5 ghz band is saturated . as a result , the wireless unit of 5 ghz band in the 5 ghz - band is incapable of receiving a signal that should be received originally . on the other hand , as illustrated in fig1 b , there is a case , in which the positions of the feeder line 4 b and the split portion 5 b are interchanged in such a manner that the split portion 5 b of the 5 ghz - band sr resonator antenna 20 is disposed near the position where the 2 . 4 ghz - band sr resonator antenna 10 is disposed . in this case , even when a signal of a frequency in 2 . 4 ghz band that is input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 leaks to the 5 ghz - band sr resonator antenna 20 , the signal bypasses the split portion 5 b , and is supplied to the feeder line 4 b , while being attenuated by the bypass route indicated by the dotted - line arrow . since the slit portion 5 b is adjusted to resonate at a frequency in 5 ghz band , the electrostatic capacitance may be small for a signal of a frequency in 2 . 4 ghz band . when the slit portion 5 b is observed from a signal of a frequency in 2 . 4 ghz band to be output from the 2 . 4 ghz - band sr resonator antenna 10 , the slit portion 5 b is considered in an open state . therefore , it is difficult for the signal to pass through the slit portion 5 b . on the other hand , it is easy for a signal of a frequency in 2 . 4 ghz band to pass through the bypass route , which is schematically illustrated by the dotted - line arrow in fig1 b , as compared with the slit portion 5 b . fig1 illustrates isolation characteristics of the sr resonator antennas having the configuration as illustrated in fig1 b . fig1 is a diagram illustrating characteristics when the positions of the split portion 5 b and the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 are interchanged in order to improve isolation characteristics of the 2 . 4 ghz - band sr resonator antenna 10 at a frequency in 2 . 4 ghz band according to the third exemplary embodiment . fig1 is also a diagram illustrating isolation characteristics representing a ratio of output power with respect to input power of a signal to be output from the feeder line 4 b of the 5 ghz - band sr resonator antenna 20 when a signal is input from the feeder line 4 a of the 2 . 4 ghz - band sr resonator antenna 10 in the aforementioned case . the following is a case , in which comparison is made between fig1 illustrating isolation characteristics of the sr resonator antenna before the positions of the feeder line 4 b and the split portion 5 b of the 5 ghz - band sr resonator antenna 20 are interchanged described in the second exemplary embodiment referring to fig9 , and fig1 . in this case , isolation characteristics at a frequency in 2 . 4 ghz band are improved by about 5 db from about − 17 db before improvement to about − 22 db after improvement . thus , it is clear that 20 db as a target value is satisfied . the exemplary embodiment has a further advantage such that it is possible to reduce leakage of a signal from a lower frequency band sr resonator antenna to a higher frequency band sr resonator antenna . this is because interchanging the positions of the feeder line 4 b and the split portion 5 b of a higher frequency antenna makes it possible to attenuate leakage of a signal from a lower frequency antenna by bypassing leakage of the signal from the lower frequency antenna . as described above , the present invention has been described by way of the aforementioned exemplary embodiments as representative examples . the present invention , however , is not limited to the exemplary embodiments . more specifically , it is possible to apply various modifications comprehensible to a person skilled in the art within the scope of the present invention . this application claims the priority based on japanese patent application no . 2013 - 031233 filed on feb . 20 , 2013 , and all of the disclosure of which is hereby incorporated .