continuing with reference to the drawings , wherein like components are designated by like reference numerals , fig4 schematically illustrates one preferred embodiment 50 of a digitally modulated diode - pumped solid - state laser in accordance with the present invention . laser 50 is similar to laser 10 of fig1 but includes additional elements including sensor 62 for monitoring current delivered from diode - laser current source 32 to diode - laser 16 . it should be noted , here , that , as discussed above , the combination of the laser resonator and external frequency convertor could be replaced by an intra - cavity frequency - converted resonator without departing from the spirit and scope of the present invention . a current regulator 60 is responsive to a signal 63 from the current sensor , a signal 57 from a set - current generator 56 and digital modulation input signal 36 . the set - current generator signal 57 is switchable , depending on the operational state of the laser , between a current limit input signal 59 and a value which is function of the set power input 29 . the switching is accomplished by the output of a combination of a comparator 52 and a latch 54 . a signal combiner 58 provides that diode - laser current source 32 can be controlled by a signal 65 from diode current regulator 60 or signal 30 from light regulator 28 a . fig5 depicts more detail of the circuitry of fig4 . here , light regulator 28 a is configured similar to light regulator 28 of fig2 , with an exception that regulator 28 a includes a switch 74 operable by the output of comparator 52 and latch 54 to switch the regulator into an inactive ( buffer ) mode via a loop 75 . current regulator 60 is configured similar to light regulator 28 a and includes a switch 76 operable by the digital modulation input signal for activating or deactivating the regulator . the current regulator includes an operation amplifier 80 , resistors r 4 , r 5 , and r 7 , and a capacitor c 2 . a series combination of resistor r 5 and capacitor c 2 has the same feedback - loop function as resistor r 3 and capacitor c 1 in the light regulator . resistor r 4 prevents the output of set current generator 56 from being shorted to ground by switch 76 . resistor r 7 determines the gain of the current regulator in combination with r 5 and c 2 . current sensor 62 functions by converting sensed current to a voltage across a resistor r 8 and amplifying the voltage using an amplifier 85 . signal combiner 58 combines the output of the light regulator and the current regulator into a current - source driving - signal 88 using diodes d 1 and d 2 and a pull - up resistor r 6 . due to the polarity of the diodes a low voltage signal at the output of any one of the regulators will pull down the current source driving signal 88 . set - current generator 56 includes a switch 72 operated by the output of comparator 52 and latch 54 . switch 72 switches the output between the current limit input and a value generated from the set power input by an arithmetic unit 86 . detector calibration unit 26 is configured as described above with reference to the circuitry of fig2 . fig6 a , fig6 b , fig6 c , and fig6 d form a timing diagram schematically illustrating operation of laser 50 over one cycle of digital modulation from an “ off ” state to an “ on ” state at time t 0 and from the “ on ” state back to the “ off ” state at time t 1 . a description of this operation is set forth below with reference to the timing diagram of fig6 a - d and with reference in addition to the circuitry of fig4 , and fig5 . in a general description of the inventive digital modulation method , when digital modulation is switched on at time t 0 ( see fig6 a ), the diode - laser current is allowed to rise toward a set value calculated by the arithmetic unit 86 ( see fig6 b ). the calculated current set value is determined by an addition of a constant offset value and a fraction of the set - power value . this is discussed further herein below . the slope of the current rise is determined by the time - constant of the regulator , which is determined , here , by the values of r 5 and c 2 . after the laser build up time is passed , the laser power begins to rise quickly corresponding to the high current value that has been reached at that time . while the current is rising , in a current regulation mode , the laser power is monitored . when the monitored power reaches the set power , the current - rise is interrupted and control of the diode - laser current is transferred to a light - regulation mode in which the light regulator controls the current supply to provide whatever current is necessary to maintain the laser output power at a constant level . in fig6 b , the current is depicted as falling while the power stays constant . this is due to thermal effects as the laser stabilizes . the fall of the current is exaggerated in fig6 b for convenience of illustration . at time t 1 , the diode current is cut off , laser power falls and the light - regulation period is terminated . in a detailed description of the inventive method , with reference in particular to the circuitry of fig5 , in the “ off ” state of the laser , the diode - laser current is ( or has been ) switched off by the digital modulation input . accordingly , there is no diode - laser current sensed by current sensor 62 . switch 74 has set light regulator 28 a to a buffer mode as indicated in fig5 . the modulation input has caused switch 76 to set the input to current regulator 60 to zero volts as indicated in fig5 . this leads to a low voltage output of the current regulator . the output of photodiode 24 is also zero , as laser radiation is not being generated . the comparator / latch ( 52 / 54 ) output has been set to zero by the digital modulation input . in order to start an “ on ” cycle of the laser , the digital modulation input is raised from low ( digital zero ) to high ( digital one ) with the comparator / latch output remaining , initially , at zero . this digital modulation input enables the diode - laser current - source , corresponding to input from current regulator 60 . switch 76 opens and transmits the set - current signal from set - current generator 56 to current regulator 60 . this set - current signal is calculated by arithmetic unit 86 of the set current - generator from the set power value and an additional offset value according to a predetermined function of the laser set power as a function of diode current . the predetermined function can be readily determined by experiment for any laser . the offset value provides that the calculated value is higher than the highest anticipated current - value required for the set power level , but is less than the current - limit . the diode - laser current rises , as the current regulator is not stabilized , and the set - current value is higher than the actual current being monitored by current - sensor 62 . the comparator / latch combination is activated by the digital modulation input rise from low to high , and begins to compare the set power input signal with the output of laser power monitor 26 ( the actual power ). when the actual power reaches the set power , the output of comparator 52 will toggle from low to high ( digital 0 to digital 1 , see fig6 d ) and the value will be stored by latch 54 until digital modulation goes from high to low ( the end of the modulation cycle ). the toggling of the comparator changes the status of switches 72 and 74 . changing the status of switch 72 switches the set current for the current regulator from the value calculated by arithmetic unit 86 to the current - limit input value . changing the status of switch 74 activates the light regulator by switching the regulator from the buffer mode to a free regulator mode . signal combiner 58 combines signals 30 ( from the light regulator ) and 65 from the current regulator in such a way that signal 88 transmitted to diode - laser current source 32 is a function of the minimum value of signals 30 and 65 . this means that , provided signal 30 never commands a current above the current set limit , control of the current supply will be only by light regulator 28 a , with the current regulator only functioning as a current limiter to protect the laser - diode from excess current . in this condition , the laser can be defined as having been switched by the comparator from the current regulation mode to a light regulation mode . as this mode - switch occurs essentially instantaneously , at a time when the set power and actual power are equal , the slight overshoot of laser power at the beginning of the light regulation mode period ( see fig6 c ) is minimized . further , as the light regulator is only activated when the actual power is equal to the set power the value of feedback capacitor c 1 can be much lower than in the prior art regulator of fig2 . this provides for a much faster regulation response time which would allow for fast analog modulation ( if desired ) during an “ on ” period . output noise , particularly at higher modulation frequencies is also considerably reduced by the use of the smaller capacitor value . at the end of the digital modulation cycle , the digital modulation input signal goes from high to low . this disables current supply 32 and the current set point is switched back to zero by switch 76 . the state of the comparator / latch combination is reset to low ( digital zero ) which changes back the status of switches 72 and 74 putting the light regulator back in a buffered state , and the set - current generator ready for current regulation at the beginning of a next digital modulation cycle . it can be seen from fig6 c , that the inventive arrangement and operating method of laser 50 , wherein laser output power is controlled first by a current regulator and then by a light regulator , provides that stabilized power at low and high set values begins to be delivered a very short time after the laser build up time has elapsed . this , in turn , provides that , for any chosen duration of a modulation cycle , stabilized power is delivered over a greater portion of the modulation cycle than in a prior - art laser in which laser output power is controlled entirely by a light regulator . further , the portion of the modulation over which the stabilized power is delivered is only weakly dependent on the peak laser power . what dependence there is the opposite of that of the prior - art laser , with stabilized power being reached slightly faster for lower peak power than it is reached for higher peak power . by way of example , the above - described laser intra - cavity frequency - doubled ops laser , which required 200 μs for stabilization at 2 mw set power compared with about 20 μs for stabilization at 20 mw set - power , was modified with the additional circuitry and components of fig4 and fig5 . at set power levels of 20 mw , 10 mw , 5 mw , and 2 mw , stabilization times were 24 μs , 20 μs , 16 μs , and 18 μs , respectively . in the circuitry of fig5 , values for r 2 , r 3 , r 4 , r 5 , r 6 , r 7 , and r 8 were 1000 ohms , 10 ohms , 1000 ohms , 10 ohms , 1000 ohms , 10 , 000 ohms , and 0 . 1 ohms , respectively . values for c 1 and c 2 were 3 . 3 nanofarads and 100 picofarads , respectively . diodes d 1 and d 2 were each type 1ps76sb10 diodes , available from philips nv of eindhoven , holland . it should be noted , here , that functional electronic circuitry described above for implementing the inventive method of operation of a digitally modulated diode - pumped solid - state laser is merely one example of such circuitry . those skilled in the electronic art , from the description of the present invention provided herein may devise other circuitry for implementing the inventive operation method without departing from the spirit and scope of the present invention . in summary , the present invention is described above with reference to a preferred embodiment . the invention , however , is not limited to the embodiment described . rather , the invention is limited only by the claims appended hereto .