CROSS-REFERENCE TO RELATED APPLICATIONS 
       [0001]    The present application claims the benefit of priority to U.S. Provisional Patent Application No. 61/900,989 filed Nov. 6, 2013, entitled “Touch Recognition Method and Noise Reduction Method thereof”, and Taiwan patent application No. 102146566 and No. 102146568 filed Dec. 17, 2013, entitled “Touch Sensitive Control Device and Electronic Apparatus and Method Thereof”, the benefit of priority of each of which is claimed hereby, and each of which are incorporated by reference herein in its entirety. 
     
    
     FIELD OF THE INVENTION 
       [0002]    The present invention pertains to a touch-sensitive screen, and more particularly pertains to a noise handling method for touch detection in a touch-sensitive screen. 
       BACKGROUND OF THE INVENTION 
       [0003]    A touch-sensitive screen enables the users to interact directly with what is displayed, and it becomes a popular user interface and is used widely in a variety of applications including automotive, aviation, marine, and consumer electronic applications, e.g. smartphone, tablet PC etc. There are a variety of touchscreen technologies that have different methods of sensing touch, including but not limited to, resistive type, surface capacitive type, projected capacitive type, infrared type, surface acoustic wave, and so on. 
         [0004]    General speaking, mostly the methods of sensing touch are more or less susceptible to outside electromagnetic interference except the sensing touch methods of infrared and surface acoustic wave. While the present invention will be described in conjunction with a capacitive touch-sensitive apparatus, it will be understood that the descriptions are not intended to limit the present invention to this kind of touch sensing apparatus. On the contrary, a touch-sensitive apparatus using other types of touch sensing may apply the spirit of the present invention. 
         [0005]    The sensing principle of projected capacitive touch apparatus are operated by measuring tiny changes in capacitance on an electrode due to a proximity or a touch (hereinafter called “proximity”) upon a touch apparatus caused by a human fingers or other objects. While electronic products are increasingly used in modern life, the effect of electromagnetic noise radiated by those electronic products is of growing concern. The interference voltages are coupled capacitively from electromagnetic noise sources that are both internal and external to the projective capacitive touch device. These interference voltages cause charge movement within the projected capacitive touch apparatus, which may be confused with the measured charge movement due to proximity upon the touch apparatus by a human fingers or other objects. The probability of identifying false touches by a touch control system of a projective capacitive touch screen will increase especially when the operating frequency of the projected capacitive touch apparatus is quite close to that of undesired electromagnetic noise. 
         [0006]      FIG. 1  is a sinusoidal waveform diagram illustrating external electromagnetic waves in accordance with an embodiment of the present invention. As shown in  FIG. 1 , there are two example waveforms  110  and  102  which are sinusoidal noise with distinct frequency and amplitude. The interference voltages are coupled capacitively from electromagnetic noise sources  110  and/or  102  to a projective capacitive touch device during a proximity event caused by a user. For the projective capacitive touch device, the electromagnetic noise sources  110  and/or  102  are unknown. In other words, it is difficult to anticipate for the touch control system of the projective capacitive touch about the measured charge variation how much amount coupled from electromagnetic noise sources  110  and/or  102 . 
         [0007]    Accordingly, there is a need in the art about a proximity detection method, a touch-sensitive control device, and a touch sensitive apparatus against external electromagnetic interference, especially sinusoidal noise, to improve accuracy of proximity detection operation. 
       SUMMARY OF THE PRESENT INVENTION 
       [0008]    In an embodiment of the present invention, there is provided a method operable in a touch-sensitive apparatus for measuring noise, wherein the touch-sensitive apparatus comprises a touch-sensitive module having a plurality of first electrodes and a plurality of second electrodes that intersect in multiple regions of the touch sensitive module, said method comprising the steps of: disconnecting the first electrodes from a driving voltage source; and acquiring a plurality of voltage values of noise by measuring a plurality of voltage signals associated with the second electrodes over a plurality of measurement cycles at a predetermined operating frequency during the first electrodes without a driving voltage. 
         [0009]    In another embodiment of the present invention, there is provided a control module operable in a touch-sensitive apparatus for measuring noise, wherein the touch-sensitive apparatus comprises a touch-sensitive module having a plurality of first electrodes and a plurality of second electrodes that intersect in multiple regions of the touch sensitive module, said control module comprising: a driving control module for disconnect the first electrodes from a driving voltage source; and a noise measurement module for acquiring a plurality of voltage values of noise by measuring a plurality of voltage signals associated with the second electrodes over a plurality of measurement cycles at a predetermined operating frequency during the first electrodes without a driving voltage. 
         [0010]    In still another embodiment of the present invention, there is provided a touch-sensitive apparatus comprising a touch sensitive module configured to receive and response fingers or hands of users in the close proximity of the surface, wherein the touch sensitive module comprises a plurality of first electrodes and a plurality of second electrodes that intersect in multiple regions; and a touch control module connected to the touch sensitive module and operable for measuring external noise of the touch-sensitive module to select an optimal measurement mode for proximity detection operation, said touch control module comprising: a driving control module for disconnect the first electrodes from a driving voltage source; and a noise measurement module for acquiring a plurality of voltage values of noise by measuring a plurality of voltage signals associated with the second electrodes over a plurality of measurement cycles at a current operating frequency during the first electrodes without a driving voltage. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0011]      FIG. 1  is a sinusoidal waveform diagram illustrating external electromagnetic waves in accordance with an embodiment of the present invention. 
           [0012]      FIG. 2  is a block diagram illustrating an electronic system with touch function in accordance with an embodiment of the present invention. 
           [0013]      FIG. 3  is a flowchart illustrating a method for determining a coordinate position in response to a proximity detection for a touch-sensitive apparatus in accordance with an embodiment of the present invention. 
           [0014]      FIG. 4  is a sinusoidal waveform diagram illustrating one of the measured noise signals in accordance with an embodiment of the present invention. 
           [0015]      FIG. 5  is a waveform diagram associated with  FIG. 4  illustrating the second electrodes are driven by a constant voltage during noise measurement phase in accordance with an embodiment of the present invention. 
           [0016]      FIG. 6A  is a diagram of noise strength with respect to phase difference of noise illustrating different graphs about noise strength respectively for three measurement modes in accordance with another embodiment of the present invention. 
           [0017]      FIG. 6B  is a diagram of minimum noise strength with respect to phase difference of noise based on three measurement modes for measurement operation shown in  FIG. 6A . 
           [0018]      FIG. 7A  is a test result from line drawing experiment with two fingers. 
           [0019]      FIG. 7B  is another test result from line drawing experiment with two-finger touch. 
           [0020]      FIG. 8  is a diagram of noise strength with respect to phase difference of noise about measurement mode W and the 4 th  measurement mode. 
           [0021]      FIG. 9  is a flowchart illustrating a method for determining a coordinate position in response to a proximity detection for a touch-sensitive apparatus in accordance with another embodiment of the present invention. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0022]    Reference will now be made in detail to embodiments of the present invention, examples of which are illustrated in the accompanying drawings. While the present invention will be described in conjunction with embodiments, it will be understood that the descriptions are not intended to limit the present invention to these embodiments. On the contrary, the descriptions are intended to cover alternatives, modifications and equivalents, which may be included within the spirit and scope as defined by the appended claims. Furthermore, in the following detailed description, numerous specific details are set forth in order to provide a thorough understanding of embodiments of the present invention. However, one of ordinary skill in the art will understand that embodiments of the present invention may be practiced without these specific details. In other instances, well known methods, procedures, components, and circuits have not been described in detail as not to unnecessarily obscure aspects of the present invention. 
         [0023]    Referring to  FIG. 2 , there is shown a block diagram which illustrates an electronic system  200  with touch function in accordance with an embodiment of the present invention. The electronic system  200  can include a touch-sensitive module  210 , a touch control module  220  connected to the touch-sensitive module  210 , and a central processor  230  connected to the touch control module  220 . However, one of ordinary skill in the art would understand that the electronic system  200  can include other unrelated components, for the purpose of simplicity, not depicted in the drawings. 
         [0024]    According to one embodiment, the touch-sensitive module  210  can be a part of a touch screen, or a part of a touch keyboard/keypad. The touch-sensitive module  210  generally includes a substrate, but not limited to, on which a plurality of first electrodes  211  arranged in a first direction and a plurality of second electrodes  212  arranged in a second direction are formed. Depending on the design, functionality, and performance requirements, a few to hundreds of electrode intersections formed by the first electrodes  211  and the second electrodes  212  are disposed. The first electrodes  211  and the second electrodes  212  are respectively coupled to the touch control module  220 . The type of their connection or coupling to the touch control module  220  is not required as shown in  FIG. 2 . The present disclosure does not limit the type of connections or coupling. If the touch-sensitive module  210  belongs to a type of projected capacitive touch, mutual capacitances existing between the first electrodes  211  and the second electrodes  212  at locations where they intersect, such mutual capacitances changing in the presence of one or more fingers or touch devices brought into proximity thereto. Therefore, a touch or a close proximity event is then sensed by changes in the electrical field at the intersection with the touch control module  220 . 
         [0025]    The touch control module  220  can include, but not limited to, logic circuits, an embedded processor, and/or a signal processor. The processor can download a program from a non-volatile memory  222 , and the processor can read an electronic signal. The aforementioned program and electronic signal are utilized to control the first electrodes  211  and the second electrodes  212  for detecting a proximity event of fingers. The code of implementation of the present disclosure is also included in the program. In one embodiment, the touch control module  220  and the non-volatile memory  222  can be integrated together in a single IC (integrated circuit) chip. In another embodiment, the touch control module  220  and the non-volatile memory  222  can reside separately in different IC chips. The connection depicted in the drawings between the touch control module  220  and the non-volatile memory  222  is not required to be direct, as shown in  FIG. 2 . 
         [0026]    The central processor  230  can execute the operating system and functions of the electronic system  200 , and the central processor  230  can receive these trigger signals from the touch control module  220 . These trigger signals are used to notify the proximity event occurred on the touch-sensitive module  210 . In one embodiment, the central processor  230  and the touch control module  220  can be integrated together in a single IC chip. In another embodiment, the central processor  230  and the touch control module  220  can reside separately in different IC chips. The connection depicted in the drawings between the central processor  230  and the touch control module  220  is not required to be direct, as shown in  FIG. 2 . 
         [0027]      FIG. 3  is a flowchart illustrating a method for determining a coordinate position in response to a proximity detection for a touch-sensitive apparatus in accordance with an embodiment of the present invention. While touch sensing systems are designed to only measure signals related to a user&#39;s proximity, noise signals generated from AC/DC chargers, liquid crystal displays, and so forth, so the touch signals cannot be properly measured. Accordingly, a noise handling and mode selection method is herein described, and it is not about noise cancelling but identifying an optimal measurement mode for measurement operation with noise suppression effect, especially for sinusoidal noises. As mentioned above, according to one embodiment, the method  300  can be implemented in the form of programs stored into non-volatile memory  222  and executed by the central processor  230  which is embedded in the touch control module  220 . Alternatively, according to another embodiment, the method  300  can be implemented in the form of logic circuits. 
         [0028]    In this embodiment, the method is executed in a manner of iteration to select an optimal measurement mode for measurement operation, which can reduce noise interference from sinusoidal noise. The method may begin at a periodic proximity detection on a touch-sensitive apparatus  200 , and a proximity event on a touch-sensitive apparatus  200  has been detected (block  310 ). The coupled noise induced on a touch-sensitive module  210  may cause the touch control module  220  to identify false touches or determine incorrect touch locations. To design optimal measurement modes for measurement operation with noise suppression effect, firstly the noise measurements are made (block  320 ). In one embodiment, the noise measurements are based on measurement by charge transfer, that is, measurement of induced charge from extraneous noise, for example, on a capacitances existing between the first electrodes  211  and the second electrodes  212  at locations where they intersect. 
         [0029]    The noise measurement is analogous to a signal measurement but without driving voltage supplied to the first electrodes  211 . The touch control module  220  stops supplying a driving voltage to the first electrodes  211 , and make the second electrodes  212  configured in a floating potential and measured for multiple times during a predetermined period of time, thereby a plurality of measurement results obtained. Without applying a driving voltage to the first electrodes  211 , there is no induced electric field between the first electrodes  211  and the second electrodes  212 . Under this situation, the measured results on the second electrodes  212  are not influenced even though a proximity of a body or fingers occurs. In another word, the induced charges on the second electrodes  212  only comes from coupled noise, and the measured voltages on the second electrodes  212  are results of charge integration since the second electrodes  212  is configured in a floating potential. In this manner, the noise measurements can be implemented. Since the same circuit elements and interconnects are used for measurement, the noise measurements can be made without any additional hardware requirement for the touch control module  220 . 
         [0030]    After a plurality of measurement results, i.e. voltage values, are acquired over a plurality of measurement cycles (block  320 ), the method proceeds to calculate individual noise impact (alternatively called evaluation of noise) for each measurement mode among multiple designed measurement modes at the current operating frequency (block  330 ) according to the measured voltage values of noise. Each of the plurality of designed measurement modes corresponds to a combination of a plurality of forward operations and a plurality of reverse operations. Based on various and defined order composed by a plurality of “forward” measurement operations and a plurality of “reverse” measurement, the plurality of designed measurement modes can be formed. The so-called “forward” and “reverse” measurement operations, which measure voltage output in response to proximity detection, have been disclosed in U.S. patent application Ser. No. 14/486,049, titled “TOUCH RECOGNITION METHOD AND SYSTEM FOR A CAPACITIVE TOUCH APPARATUS”, filed Sep. 15, 2014. it will be understood by those skilled in the art that the measured voltage output in response to “forward” and “reverse” measurement operations about a proximity of fingers has a reverse voltage output, however, the noise impact, which has gone through calculation and ends up with an absolute value, can be treated as the same regardless of “forward” or “reverse” measurement operations. 
         [0031]    Electromagnetic noise is induced on capacitive touch apparatus from a variety of sources, and herein the present invention focuses on reducing false measurement results caused by a sinusoidal noise with waveform characteristic such as  110  and  102  shown in  FIG. 1 . According to a feature of sinusoidal noise, the same sinusoidal noise can cause a different noise strength by different measurement modes in use. Accordingly, individual noise strength for each measurement mode at a certain operating frequency is calculated. 
         [0032]    When the process of the noise impact (alternatively called evaluation of noise) versus the designed measurement modes in block  330  is completed, the method proceeds to the block  340 . A step of comparing the evaluations of noise with a threshold value and check whether at least one evaluation of noise corresponding with the designed measurement modes is below a threshold value (block  340 ). Namely, a determination can be made on whether at least one of the measurement modes is acceptable (block  340 ). If at least one of the evaluation of noise corresponding with a certain measurement mode is below a threshold value (YES from block  340 ), it is determined that at least one acceptable measurement mode has been found. If none of the evaluation of noise corresponding with a certain measurement mode is below a threshold value (NO from block  340 ), it is determined that all the measurement modes are unacceptable at a current operating frequency. In other words, the method proceeds to block  350  when there is at least existing one measurement mode with acceptable noise impact. If not so, the operating frequency of the touch control module  220  is modifies (block  380 ). 
         [0033]    An optimal measurement mode is selected from among all measurement modes with acceptable noise impact (block  350 ), the guidelines of measurement mode selection as a working measurement mode for operation herein does not only depend on a measurement mode which has a minimum noise impact among all measurement modes but also take stability of noise impact into consideration. 
         [0034]    When the process of selecting a measurement mode for measurement operation in block  350  is completed, the method proceeds to block  355 . The optimal measurement mode is assigned as the working measurement mode for operation (block  350 ). According to the working measurement mode corresponding with a combination of a plurality of forward operations and a plurality of reverse operations, the touch control module  220  can control the first electrodes  211  connected to the driving voltage source and make the second electrodes  212  operated in the specific and defined order of the selected measurement mode. Then, the optimal measurement mode is assigned to be the working measurement mode for proximity detection, so the proximity detection is performing in use of the working measurement mode (block  360 ). Ultimately, the coordinates of the touched position are calculated based on the reporting results obtained with the working measurement mode when a proximity event has been detected (block  370 ). 
         [0035]    If there is no any measurement mode which suffers merely insignificant noise impact, i.e. noise impact is above or equal to a noise threshold at the current operating frequency, the operating frequency of the touch control module  220  is required to be modified, e.g. to be decreased (block  380 ). Then, the touch control module  220  may be configured to return back to block  320  for execution of next iteration. Generally, the preset operating frequency is the maximum frequency that the touch control module  220  can work in order to have a fast reporting for proximity detection on the touch-sensitive apparatus  200 . In the following description, the noise measurements mentioned in block  330  and the calculation process of the noise impact versus the designed measurement modes mentioned in block  330  will be described in details. 
         [0036]    In accordance with an embodiment of the present invention,  FIG. 4  is a sinusoidal waveform diagram illustrating one of the measured noise signals. Referring to  FIG. 4 , the sinusoidal noise waveform herein may be indicative of the noise signal  110  or  102  as shown in  FIG. 1 , or any quasi-sinusoidal noise signal. It is noted that a signal at a given time point has a different phase at distinct frequency. There is a phase difference existing between a measurement signal and a sinusoidal noise signal. Providing that the sinusoidal noise signal is viewed as a sinusoidal wave  110 , and the measured noise signal is just right in the beginning of a period at time  400  in  FIG. 4 . A person of ordinary skill in the art would understand that the noise signal  110  can be viewed as a co-sinusoidal wave. Assuming that the phase of the measured noise is viewed as 0 at time  400 , the phase of the measured noise phase is viewed as θ at time  410 . Because the amplitude and frequency of the noise signal  110  are unknown during noise measurement operation, provided that a phase difference for the noise signal  110  between two given time, i.e. ψ or 2πk+ψ, when measurement operation is conducted respectively at time  420  and  430 , where k is integer, and k&gt;=0. 
         [0037]      FIG. 5  is a voltage waveform diagram associated with  FIG. 4  illustrating the second electrodes  212  to be driven by a constant voltage during noise measurement in accordance with an embodiment of the present invention. As mentioned above, the first electrodes  211  disconnected from a driving voltage source when the noise measurement is performed in block  320 , the second electrodes  212  are configured in a floating potential to receive charge transfer from noise and the integrated amount of charge transfer or capacitances are read out afterwards. As shown in  FIG. 5 , there are totally four measurement cycles in a certain measurement mode, i.e. M1, M2, M3, and M4. Respectively at time −Td, −Tb, Ta, and Tc, the electrodes  212  are connected to a constant voltage, i.e. floating potential, and the amount of charge transfer or capacitances from noise are read out, afterwards, respectively at time −Tc, −Ta, Tb, and Td. The second electrodes  212  are reset to be configured in a ground potential upon completion of acquiring the voltage value of noise at time −Tc, −Ta, Tb, and Td. 
         [0038]    In one embodiment, the four measurement cycles, i.e. M1, M2, M3, and M4, are performed at the same operating frequency, simultaneously, assuming that the interval between each of them has the same duration. In other words, provided that charging starts at time Ta and discharging starts at time Tb, the duration of charging can be, for example but not limited, the same as the duration of discharging. Referring to  FIG. 5 , assuming that the measured noise at the middle of measurement cycle M2 and M3, i.e. time  410 , with phase θ corresponds to the sinusoidal noise at the time  410  as shown in  FIG. 4 . Besides, the contiguously measured noise signal at time Tb and Td exists a phase difference, i.e. or 2πk+ψ, where k is an integer, and k&gt;=0. The time Tb and Td which correspond respectively to time  420  and  430  as shown in  FIG. 4 . 
         [0039]    During noise measurement in block  320 , the measured voltage value at each time point shown in  FIG. 5  can be represented by the following equations with sinusoidal waveform characteristic. If X=(2πk+ψ)/4, substitute X into all equations: 
         [0000]        Ta=A  sin(θ+(2 πk +ψ)/4)= A  sin(θ+ X )
 
         [0000]        Tb=A  sin(θ+3×(2 πk +ψ)/4)= A  sin(θ+3 X )
 
         [0000]        Tc=A  sin(θ+5×(2 πk +ψ)/4)= A  sin(θ+5 X )
 
         [0000]        Td=A  sin(θ+7×(2 πk +ψ)/4)= A  sin(θ+7 X )
 
         [0000]      − Ta=A  sin(θ−(2 πk +ψ)/4)= A  sin(θ− X )
 
         [0000]      − Tb=A  sin(θ−3×(2 πk +ψ)/4)= A  sin(θ−3 X )
 
         [0000]      − Tc=A  sin(θ−5×(2 πk +ψ)/4)= A  sin(θ−5 X )
 
         [0000]      − Td=A  sin(θ−7×(2 πk +ψ)/4)= A  sin(θ−7 X )
 
         [0040]    Where A represents the amplitude of the measured noise signal having a sinusoidal signal characteristic, and A does not represent the amplitude of the input noise signal  110  or  102  shown in  FIG. 1 . 
         [0041]    At each measurement cycle, the noise strength, which is about the amount of noise charge transfer caused by a noise signal, is related to the charging start location in a measurement cycle and the voltage read out in a measurement cycle. For example, in measurement cycle M3, charging starts at time Ta and discharging at time Tb so the measured voltage value of noise is influenced by the amount of noise at time Ta and Tb. The voltage value of noise integrated upon completion of each measurement cycle, i.e. M1, M2, M3, and M4, can be represented respectively by the following equation: 
         [0000]        M 1 =A  sin(θ−7 X )− A  sin(θ−5 X )
 
         [0000]        M 2 =A  sin(θ− X )− A  sin(θ−3 X )
 
         [0000]        M 3 =A  sin(θ+3 X )− A  sin(θ+ X )
 
         [0000]        M 4 =A  sin(θ+7 X )− A  sin(θ+5 X )
 
         [0042]    According to one exemplary embodiment, the first measurement mode for measurement operation is defined with an order in sequence, e.g. “forward operation”, “reverse operation”, “forward operation” and “reverse operation”. As mentioned above, the measured voltage output in response to “forward” and “reverse” operations about a proximity detection has a reverse voltage output. As a result, the amount of noise accumulated upon completion of the first measurement mode for measurement operation can be represented by (M2−M1)+(M4−M3) which can be represented by the following equation: 
         [0000]      ( M 2 −M 1)+( M 4 −M 3)= A [sin(θ− X )−sin(θ−3 X )−sin(θ−7 X )+sin(θ−5 X )+sin(θ+7 X )−sin(θ+5 X )−sin(θ+3 X )+sin(θ+ X )]  Equation (1)
 
         [0043]    Noted that sin(θ−X)+sin(θ+X)=2 sin θ cos X, so Equation (1) can be simplified to: 
         [0000]      ( M 2 −M 1)+( M 4 −M 3)=2 A  sin θ(cos  X −cos 3 X −cos 5 X +cos 7 X )  Equation (2)
 
         [0044]    It is noted that cos X+cos 7X=2 cos 4X cos(−3X)=2 cos 4X cos 3X, cos 3X+cos 5X=2 cos 4X cos(−X)=2 cos 4X cos X, so Equation (2) can become: 
         [0000]    
       
         
           
             
               
                 
                   
                     
                       
                         
                           
                             
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         [0045]    According to another exemplary embodiment, the second measurement mode for measurement operation is defined with an order in sequence, e.g. “forward operation”, “reverse operation”, “reverse operation” and “forward operation”. As a result, the amount of noise accumulated upon completion of the first measurement mode for measurement operation can be represented by (M2−M1)+(M3−M4) which can be represented by the following equation: 
         [0000]      ( M 2 −M 1)+( M 3 −M 4)= A [sin(θ− X )−sin(θ−3 X )−sin(θ−7 X )+sin(θ−5 X )+sin(θ+3 X )−sin(θ+ X )−sin(θ+7 X )+sin(θ+5 X )]  Equation (4)
 
         [0046]    Noted that sin(θ−X)−sin(θ+X)=−2 cos θ sin X, so Equation (4) can be simplified to: 
         [0000]      ( M 2 −M 1)+( M 3 −M 4)=−2 A  cos θ(sin  X −sin 3 X −sin 5 X +sin 7 X )  Equation (5)
 
         [0047]    Noted that sin X+sin 7X=2 sin 4X cos(−3X)=2 sin 4X cos 3X, sin 3X+sin 5X=2 sin 4X cos(−X)=2 sin 4X cos X, so Equation (5) can become: 
         [0000]    
       
         
           
             
               
                 
                   
                     
                       
                         
                           
                             
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                     6 
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         [0048]    According to still another example, the third measurement mode for measurement operation is defined with an order in sequence, e.g. “forward operation”, “forward operation”, “reverse operation” and “reverse operation”. As a result, the amount of noise accumulated upon completion of the first measurement mode for measurement operation can be represented by (M3−M1)+(M4−M2) which can be represented by the following equation: 
         [0000]      ( M 3 −M 1)+( M 4 −M 2)= A [sin(θ+3 X )−sin(θ+ X )−sin(θ−5 X )+sin(θ−7 X )+sin(θ+7 X )−sin(θ+5 X )−sin(θ− X )+sin(θ−3 X )]  Equation (7)
 
         [0049]    Noted that sin(θ−X)+sin(θ+X)=2 sin θ cos X, so Equation (7) can be simplified to: 
         [0000]      ( M 3 −M 1)+( M 4 −M 2)=2 A  sin θ(−cos  X +cos 3 X −cos 5 X +cos 7 X )  Equation (8)
 
         [0050]    Noted that cos 7X−cos X=−2 sin 4X sin(3X), cos 3X−cos 5X=−2 sin 4X sin(−X)=2 sin 4X sin X, so Equation (8) can become: 
         [0000]    
       
         
           
             
               
                 
                   
                     
                       
                         
                           
                             
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         [0051]    In summary, the aforementioned three measurement modes for measurement operation can obtain respectively the three Equations (3), (6), and (9). The right-hand side of all three equations can be generally divided into two parts. One part is related to phase θ, e.g. −8A sin θ in Equation (3) and (9), 8A cos θ in Equation (6), and the other part can be described as a function of X such as f1(X) in Equation (3), f2(X) in Equation (6) and f3(X) in Equation (9). The part related to phase θ can get a value ranging from −8 to 8 on the ground of value of sin and cos [−1,1]. The other part related to a function of X can be deemed as a function of phase difference between two time points, i.e. ψ, due to X=(2πk+ψ)/4. 
         [0052]    For any operating frequency, a phase difference of noise, i.e. W/, exists between two measured voltage values measured at two time points. Therefore, f1(X), f2(X) and f3(X) can be also represented by g1(ψ), g2(ψ) and g3(ψ), which determine noise strength of whatever frequency of noise. The aforementioned noise impact, not noise strength, can be defined only by the product of f(θ) and g(ψ) so that it is independent from the number of measurement cycle. It is observed that the part related to phase θ is also not correlated to frequency of noise but correlated to measured amplitude of noise. Accordingly, the maximum of the part related to phase θe.g. [−8 to 8] by measurement mode 1, 2, or 3 for measurement operation, can be defined as the threshold of noise strength. In other words, whether the noise impact is acceptable depends on the magnitude of the function of the phase difference, i.e. g(ψ). If the function of the phase difference, i.e. g(ψ), is below a predetermined value, the noise strength or noise impact, can be limited so as to the associated measurement mode which is acceptable for measurement operation. 
         [0053]      FIG. 6A  is a diagram of noise strength with respect to phase difference of noise illustrating different graphs about noise strength respectively for three measurement modes in accordance with another embodiment of the present invention. There are three measurement modes of measurement operation as shown in  FIG. 6A , respectively, the 4 th  measurement mode, the 5 th  measurement mode, and the 6 th  measurement mode. The exemplary embodiment in  FIG. 6A  are based on six measurement cycles, i.e. M1, M2, M3, M4, M5 and M6, in a certain measurement mode for measurement operation while the aforementioned exemplary embodiment in  FIG. 5  are based on four measurement cycles. It is appreciated that embodiments of the present invention may be practiced with eight or more measurement cycles provided that the noise phase is θ locating in the middle of these measurement cycles. According to the same manner as described in  FIG. 5 , a general measured noise strength on the right-hand side of an equations (10) can be expressed regardless of how many measurement cycles and whatever measurement mode for measurement operation operating conducted on the left-hand side of the equation (10): 
         [0000]        c*Af (θ) g (ψ)  Equation (10)
 
         [0054]    where c represents a constant value, A represents the amplitude of the measured noise signal, f(θ) represents a noise function with phase θ based on a sinusoidal (or cosinusoidal) noise signal, and g(ψ) represents a function of phase difference between any two time points of the sinusoidal noise signal. For the purpose of simplicity and clarity, assuming that the constant value, i.e., c is 16 based on six measurement cycles. 
         [0055]    Referring to  FIG. 6A , the noise strength operating by the 4 th , 5 th , and 6 th  measurement mode for measurement operation can be represented respectively by the following equations: 
         [0000]      16 A  sin θ(sin  X  sin 6 X  cos 2 X  cos 2 X )  Equation (11)
 
         [0000]      16 A  sin θ(sin  X  sin 2 X  cos 4 X  cos 4 X )  Equation (12)
 
         [0000]      −16 A  cos θ(sin  X  cos 6 X  sin 2 X  sin 2 X )  Equation (13)
 
         [0000]    The 4 th  measurement mode for measurement operation is defined with an order in sequence “forward operation”, “forward operation”, “forward operation”, “reverse operation”, “reverse operation” and “reverse operation”; the 5 th  measurement mode for measurement operation is defined with an order in sequence “forward operation”, “reverse operation”, “forward operation”, “reverse operation”, “forward operation” and “reverse operation”; the 6 th  measurement mode for measurement operation is defined with an order in sequence “forward operation”, “reverse operation”, “forward operation”, “forward operation”, “reverse operation” and “forward operation”. Take the 4 th  measurement mode for example, it is observed that the noise impact is approaching to 0 if any one of sin X, sin 6X, cos 2X, or cos 2X is approaching to 0. 
         [0056]    As shown in  FIG. 6A , the noise strength varies along with the phase difference. If only one single measurement mode is operated, a strong noise measured at a certain phase difference may result in a false measurement of proximity detection. For example, the noise strength is about 11 when the phase difference is at 180° (=π) by the operation of the 5 th  measurement mode, while the noise strength is about 0 at the same phase difference by the operation of the 4 th  measurement mode. 
         [0057]    If the operating frequency of the touch control module  220  for proximity detection is operating at 28 KHz by the 5 th  measurement mode for measurement operation, the noise signal is at 14 KHz in terms of phase difference at 180° (=π). An experiment of drawing two straight lines in a parallel with two fingers on a touch screen has been done. As shown in  FIG. 7A , the two plotted lines are not parallel at all, and it is indicative of a severe noise interference existing. Referring to  FIG. 7B , in case the operating frequency of the touch control module  220  for proximity detection is operating at 28 KHz by the 4 th  measurement mode for measurement operation, the noise signal is still at 14 KHz in terms of phase difference at 180° (=π). However, the amplitude for observation purpose is changed to be five times as large as that shown in  FIG. 7A , i.e. 15V PP  (peak-to-peak noise voltage). The two plotted lines shown in  FIG. 7B  are almost parallel, and it is indicative of only slight noise interference existing. Thus, one of ordinary skill in the art would understand that the result of noise interference is such distinct by using a different measurement mode for measurement operation against noise. In this manner to handle any other frequency of noise, the touch control system can enhance anti-noise capability by switching to a measurement mode with slight noise impact at a certain frequency of noise for measurement operation. 
         [0058]      FIG. 6B  is a diagram of minimum noise strength with respect to phase difference of noise based on three measurement modes for measurement operation shown in  FIG. 6A . As shown in  FIG. 6B , the minimum noise strength with respect to phase difference of noise is formed by taking every point of minimum noise strength with respect to every phase difference from among the three graphs representing three measurement modes for measurement operation. It can be realized that the noise strength is controlled in a limited range when a right measurement mode for measurement operation is selected among a plurality of measurement modes. 
         [0059]    In one exemplary embodiment, provided that the number of the designed measurement modes for measurement operation is N, there are M cycles required to be performed for each measurement mode so that the operations of noise measurement are totally M*N times in block  320 . For example, in the embodiment shown in  FIG. 5 , when the number of measurement cycle is four, there are totally 12 times of noise measurement to be performed. When the number of measurement modes is six, there are totally 24 times of noise measurement to be conducted in a series. In one exemplary embodiment, it includes a step of averaging noise in block  320  by taking K times of noise measurements for average. Take the example illustrated in  FIG. 6A , the measurement cycle is equal to 6, and there are 3 measurement modes, i.e. the 4 th , 5 th , and 6 th  measurement modes for measurement operation as well as taking four (K=4) times of measurement results for average. As a result, a determination of whether at least one measurement mode is with an acceptable noise impact in block  340  may spend at least 3 ms if each measurement cycle is 40 us. (40 us*3*6*4=2880 us˜=3 ms) 
         [0060]    In another exemplary embodiment, provided that the operations of noise measurement are totally only M times in block  320  when the noise impact only considers g(ψ). In this embodiment, assuming that θ is fixed and f(θ) is ignored. It is noted that the errors for evaluation of measurement modes are made when all the measurement modes for measurement operation are not uniformly correlated to either “sin θ” or “cos θ”. It will be understood by those skilled in the art that the value of sin θ and cos θ is not the same. For example, if the 1 st  and 3 rd  measurement modes which are uniformly correlated to sin θ are selected for measurement operation, in this case there are only number of M measurement operations to be conducted for a determination of whether at least one measurement mode with an acceptable noise impact. Take the example illustrated in  FIG. 6A , the measurement cycle is equal to 6, and there are 3 measurement modes, i.e. the 4 th , 5 th , and 6 th  measurement mode for measurement operation as well as taking four (K=4) times of measurement results for average. As a result, a determination of whether at least one measurement mode is with an acceptable noise impact in block  340  may spend at least 1 ms if each measurement cycle is 40 us. (40 us*6*4=960 us˜=1 ms) 
         [0061]    In another exemplary embodiment, provided that at least one measurement mode is correlated to sin θ and at least another measurement mode is correlated to cos θ. In this case, it need to conduct at least M+1 measurement operation in block  320  for evaluating noise impact with respect to measurement modes. In another word, the M measurement operations in the front of all measurement operations are taken as a basis of a measurement mode for measurement operation while the M measurement operations in the rear of all measurements are taken as a basis of another measurement mode. The two different measurement modes can be compared to determine which measurement mode is with better noise impact since the two different measurement modes have different phase. For example, the measurement cycle is equal to 6, and four (K=4) times of measurement results are taken for average. As a result, a determination of whether at least one measurement mode is with an acceptable noise impact in block  340  may spend at least 0.4 ms if each measurement cycle is 40 us. (40 us*[(6+4)−1]=360 us˜=0.4 ms) 
         [0062]    Further, if noise measurement operated via a measurement mode that takes the M measurement operations in the front of all measurement operations with phase θ while the phase is equal to θ+ψ for another measurement mode based on the M measurement operations in the rear of the all measurements. For this kind of measurement operation, a general measured noise on the right-hand side of the equations (10) can be modified as follows: 
         [0000]        c*A[f (θ)+ f (θ+ψ)] g (ψ)  Equation (14)
 
         [0063]    When ψ is approaching to 180° (≈), f(θ)+f(θ+ψ) is approaching to 0 as f(θ) is a sinusoidal or cosinusoidal function. Accordingly, the right-hand side of the equations (14) is approaching to 0. This characteristic can enhance a complementary relationship existing between measurement modes for measurement operation. 
         [0064]    For example, if a measurement mode W is designed for measurement operation based on four measurement cycles as shown in  FIG. 5 , i.e. M1, M2, M3, and M4. By taking the three measurements in the front, i.e. M1-M3, and taking the three measurements in the rear, i.e. M2-M4 to form the 4 th  measurement mode shown in  FIG. 6A . Referring to  FIG. 8 , the noise strength with respect to phase difference of noise about the measurement mode W and the 4 th  measurement mode are illustrated. The constant value, i.e. c, is correlated to the number of measurement cycles to be operated in a certain measurement mode, the noise strength corresponding with the 4 th  measurement mode having six measurement cycles is required to be adjusted for comparing with that corresponding with the measurement mode W having four measuring cycles. Therefore, noise strength of the 4 th  measurement mode dividing by 2 is shown in  FIG. 8 . It is observed that noise strength of the 4 th  measurement mode dividing by 2 is below or equal to 0.3 when the phase difference of noise is between 120° and 240°. The complementary relationship between measurement modes seems to be working out. So to speak, the 4 th  measurement mode seems having better anti-noise effect than the measurement mode W. 
         [0065]    If the g(ψ) of the measured noise strength taken from M measurement operations in the front of all measurement operations is just equal to a reverse signal of the g(W) of the measured noise strength taken from M measurement in the rear of all measurement operation, in this manner, noise can be reduced around the phase difference of noise equaling to 0° or 360°, because the measured noise strength is approaching to 0 when ψ is near 0° or 360°. 
         [0066]    Certainly, the design of measurement modes by taking from M measurement operations in the front and in the rear of all measurement operation includes, but not limited to, only one different measurement operation between the measurement modes. The general measured noise on the right-hand side of the equations (14) should be extendedly modified as follows: 
         [0000]        c*A[f (θ)+ f (θ+ n* ψ)] g (ψ)  Equation (15)
 
         [0000]    where n is an integer and n&gt;=1. 
         [0067]    A person of ordinary skill in the art would understand that according to some embodiments of the present invention, noise measurements can be made for more than M times and a variety of M measurement operations in sequence are taken for noise impact calculation versus N measurement modes. In one embodiment, noise measurements are made for (M+N−1) times and various M measurement operations in a sequence taken respectively among these (M+N−1) operations as N measurement modes. Provided that the measurement operation for (M+N−1) times are denoted as M 1 , M 2 , . . . M M+N−1 , the M measurement operations, i.e. M 1 , M 2 , . . . M M , are taken as a basis of the first measurement mode. The M measurement operations, i.e. M 2 , M 3  . . . M M+1 , are taken as a basis of the second measurement mode. The reset may be deduced by analogy, so the M measurement operations, i.e. M N , M N+1  . . . M M+N−1 , are taken as a basis of the N th  measurement mode. 
         [0068]    Referring to the  FIG. 3 , the process of selecting a measurement mode for operation in block  350  is based on the calculated noise impact (alternatively called evaluation of noise) in block  330  and decision block  340  which screens measurement modes to pick out at least one measurement mode with evaluation of noise below a noise threshold. In one embodiment, provided that the aforementioned first measurement mode, second measurement mode, and third measurement mode have been operated separately for noise measurement and with individual noise impact calculated, and an optimal measurement mode which has the minimum noise impact is selected in block  350 . It is appreciated that the noise measurement operation will be remained to be operating in the working measurement mode, e.g. the second measurement mode, but not switching to be operating in the selected measurement mode e.g. the third mode, even though the evaluation of noise corresponding with the selected is smaller than that corresponding with the working measurement mode. 
         [0069]    In still another embodiment, a mechanism of evaluating stability of measurement modes is also included in block  355 . The working measurement mode is not replaced by the selected measurement mode from decision block  340  until the method  300  has been redone continuously for a couple times and demonstrate that the selected measurement mode has an optimal noise impact than the working measurement mode in a consecutive redoing iterations for a couple time. In another word, when a plurality of evaluation of noise from a plurality of consecutive iterations corresponding with the selected measurement mode are stably smaller than the evaluation of noise corresponding with the working measurement mode, the optimal measurement mode is assigned as the working measurement mode in block  355 . 
         [0070]    As mentioned above, the noise strength corresponding with a certain measurement mode is required to be adjusted for comparing with that corresponding with another measurement mode when the number of measurement cycles is not the same between each other. In yet another embodiment, a mechanism of evaluating stability of measurement modes is also included in block  355 , the mechanism includes a step of checking whether the optimal measurement mode is the same one as the working measurement mode. If the optimal measurement mode is not the same as the working measurement mode, the method  300  goes back to redo from block  320  until the number of redoing iterations is equaling to P times, and the method  300  goes forward to assign the optimal measurement mode to be a working measurement mode when the optimal measurement mode has a better noise impact than the working measurement mode in consecutive redoing iterations for the number of redoing iterations equaling to Q times where Q is positive integer and Q&lt;P. It is appreciated that the above mentioned three embodiments are about maintenance of stability for measurement operations. In other embodiment, the mechanism of evaluating stability of measurement mode can be skipped, the optimal measurement mode which has the minimum noise impact is directly assigned as the working measurement mode in block  355 . 
         [0071]    In above description, the operating frequency for noise measurement and touch detection is required to be modified in block  380  when all of the evaluations of noise for all measurement modes at the current frequency are equal to or above a noise threshold. In one embodiment, the operating frequency for noise measurement and touch detection is decreased. Provided that the aforementioned 5 th  measurement mode is separately operated for noise measurement at 25 KHz and 20 KHz under an environment with noise at 8 KHz, the measured phase difference of noise, i.e. ψ or 2πk+ψ, is 115° at 25 KHz while the measured phase difference of noise is 144° at 20 KHz. Referring to the graph of the 5° measurement mode in  FIG. 6A , it is observed that the value of the noise strength is 0.57 when phase difference of noise=115° at 25 KHz while the value of the noise strength is 5.92 when phase difference=144° at 20 KHz. Accordingly, decreasing operating frequency for noise measurement cannot acquire a reduced noise strength. 
         [0072]    In still another embodiment, if there is noise of higher frequency in the environment such as 88 KHz, the aforementioned 5 th  measurement mode is separately operated for noise measurement at 25 KHz and 20 KHz, the measured phase difference of noise, i.e. ψ or 2πk+ψ, is 547° at 25 KHz while the measured phase difference of noise is 144° at 20 KHz. Still referring to the graph of the 5 th  measurement mode in  FIG. 6A , it is observed that the value of the noise strength is about 11 when phase difference of noise=547° at 25 KHz while the value of the noise strength is 5.92 when phase difference=144° at 20 KHz. Accordingly, decreasing operating frequency for noise measurement can reduce the noise strength from about 11 to 5.92 by using the 5 th  measurement mode for operation. 
         [0073]    Noted that the distinction between the manner of measurement mode switching from among various measurement modes and a common manner of frequency hopping from among various frequencies is that the manner of measurement mode switching adopts a fixed operating frequency in use of various measurement modes for measurement operation. As mentioned above and summarized in the following Table 1, the two frequencies 25 KHz and 20 KHz seems acceptable in term of noise strength (0.57 at 25 KHz and 5.92 at 20 KHz) when the 5 th  measurement mode is adopted for operation under an environment with noise at 8 KHz. However, when there is noise of higher frequency in the environment such as 88 KHz, the noise strength are much worse (about 11 at 25 KHz and 5.92 at 20 KHz). The two frequencies 25 KHz and 20 KHz becomes not applicable frequency to reduce noise strength, alternatively noise impact. No matter how many frequencies as operating frequency are tried, there is not an operating frequency, which can have less noise interference, namely, noise strength or noise impact with respect to any frequency of noise is all below a noise threshold. 
         [0000]    
       
         
               
               
               
               
             
               
               
               
               
             
           
               
                 TABLE 1 
               
               
                   
               
               
                   
                 Frequency 
                   
                   
               
               
                 Operating Frequency 
                 of Noise 
                 Phase Difference 
                 Noise Strength 
               
               
                   
               
             
             
               
                   
               
             
          
           
               
                 25 kHz 
                  8 kHz 
                 115.2 
                 About 1 
               
               
                 20 kHz 
                  8 kHz 
                 144 
                 About 6 
               
               
                 25 kHz 
                 88 kHz 
                 547.2 
                 About 11 
               
               
                 20 kHz 
                 88 kHz 
                 144 
                 About 6 
               
               
                   
               
             
          
         
       
     
         [0074]    From another perspective, switching measurement mode from among various measurement modes for measurement operation can reach the effect of avoiding noise interference with respect to any frequency of noise under the premise of a fixed operating frequency. For example, when the operating frequency is fixed at 25 KHz, the noise strength depending on a different measurement mode for operation with respect to frequency of noise appears not uniform as shown in the following Table 2. 
         [0000]    
       
         
               
               
               
               
             
           
               
                 TABLE 2 
               
               
                   
               
               
                   
                 Frequency 
                   
                   
               
               
                 Measurement Mode 
                 of Noise 
                 Phase Difference 
                 Noise Strength 
               
               
                   
               
             
             
               
                 4 th  Mode 
                  8 kHz 
                 115.2 
                 About 0.5 
               
               
                 5 th  Mode 
                  8 kHz 
                 115.2 
                 About 1 
               
               
                 4 th  Mode 
                 88 kHz 
                 547.2 
                 About 0.1 
               
               
                 5 th  Mode 
                 88 kHz 
                 547.2 
                 About 11 
               
               
                 4 th  Mode 
                 88 kHz 
                 547.2 
                 About 0.1 
               
               
                 5 th  Mode 
                 88 kHz 
                 547.2 
                 About 11 
               
               
                   
               
             
          
         
       
     
         [0075]    In one embodiment, the operating frequency can be divided by a variable number N where N is an integer and N&gt;1. Namely, the post-modified operating frequency is reduced to 1/N times of the pre-modified operating frequency. In a preferred embodiment, N can be six. In another embodiment, N can be a predetermined positive integer or a positive integer which is related to how high or how low the pre-modified operating frequency is. When the post-modified operating frequency appears lower than the lowest operating frequency, the operating frequency either does not be modified or is directly set to the lowest operating frequency. 
         [0076]      FIG. 9  is a flowchart illustrating a method for determining a coordinate position in response to a proximity detection for a touch-sensitive apparatus in accordance with another embodiment of the present invention. As mentioned above, according to one embodiment, the method  900  can be implemented in the form of programs stored into non-volatile memory  222  and executed by the central processor  230  which is embedded in the touch control module  220 . Alternatively, according to another embodiment, the method  900  can be implemented in the form of logic circuits. 
         [0077]    Noted that the method  900  is based on the method  300  and adds several blocks  910 ,  912 ,  920 ,  922  and  930 . As described above, the operating frequency is likely to be modified in block  380  during identifying an optimal measurement mode for measurement operation. The touch control module  220  performs method  900  which can reduce noise interference for proximity detection of fingers by a user on a touch-sensitive apparatus, starting with a default operating frequency, so these blocks are added to the method  900  to make sure the operating frequency set at the default value. Please refer to the above description for understanding the same blocks as the method  300 . The system will be unstable if the operating frequency is modified too often. For maintaining stability, the key mechanism is a counter implemented for maintaining stability of the touch-sensitive apparatus implementation, which can count up to a predetermined value, to wait for the apparatus ready to be operating at a changed operating frequency. 
         [0078]    When a proximity event has been detected in block  310 , the method proceeds to check whether the operating frequency is reset to a default value for a new iteration (block  910 ). If the touch control module  220  is operating at the default operating frequency (YES from block  910 ), the value of the counter is reset to 0 (block  912 ). If not so (NO from block  910 ), the method proceeds to check whether the value of the counter has reached the predetermined value (block  920 ). If the value of the counter has reached the predetermined value (YES from block  920 ), the touch control module  220  changes to be operating at the default operating frequency (block  930 ). Afterwards, the value of the counter is reset to 0 (block  912 ). If not so (NO from block  920 ), the value of the counter is increased (block  922 ). The method  900  proceeds to perform noise measurement (block  320 ) after the block  912  is completely executed. 
         [0079]    In block  930 , the operating frequency is restored back to the default operating frequency by raising the current operating frequency. In one embodiment, provided that the post-modified operating frequency is N times of the pre-modified operating frequency where N is a positive integer and N&gt;1. In a preferred embodiment, N can be six. In another embodiment, N can be a predetermined positive integer or a positive integer depending on the pre-modified operating frequency which is high or low to be determined. When the post-modified operating frequency appears larger than the highest operating frequency, the operating frequency can be directly set to the highest operating frequency. When the configuration of operating frequency is done, the value of the counter is reset to 0 (block  912 ). The method  900  proceed to perform noise measurement (block  320 ) after the block  912  is completely executed. 
         [0080]    A person of ordinary skill in the art would understand that the method  300  and method  900  are executed in a manner of iteration according to some embodiments of the present invention. For example, when a proximity event has been detected at each time, the following blocks in method  900  are triggered to start execution for a new iteration. After an optimal measurement mode is selected in block  350 , a step of validity checking whether the selected mode is the same one from two consecutive iterations can be included. When the selected mode from block  350  in the preceding iteration is not the same as the selected mode from block  350  in the succeeding iteration, the waveform of the driving signal supplied to the touch-sensitive module  210  based on the selected mode will be different from the block  350  in the preceding iteration and from the block  350  in the succeeding iteration. As a result, the method  900  can be executed more iterations for validation in case the selected mode is not the same from two consecutive iterations. 
         [0081]    For instance, the selected mode from block  350  in the preceding iteration is the first mode, which is defined with an order in sequence for measurement operation, e.g. “forward operation”, “reverse operation”, “forward operation” and “reverse operation”. The waveform of the driving signal supplied to the first electrodes  211  of the touch-sensitive module  210  is formed according to the first mode. Assuming that the selected mode from block  350  in the succeeding iteration is the second mode, which is defined with an order in sequence, e.g. “forward operation”, “reverse operation”, “reverse operation” and “forward operation”. As a result, the waveform of the driving signal supplied to the first electrodes  211  of the touch-sensitive module  210  is changed to be formed according to the second mode. From perspective of time, the first electrodes  211  are disconnected from the driving voltage source during the block  320  of the preceding iteration is executing, and the waveform of the driving signal supplied to the first electrodes  211  is observed according to the first mode when the block  360  in the preceding iteration is executing. Next, the first electrodes  211  are disconnected from the driving voltage source during the block  320  of the succeeding iteration is executing, and the waveform of the driving signal supplied to the first electrodes  211  is observed according to the second mode when the block  360  in the succeeding iteration is executing. Therefore, the method  900  will be redone one more iteration for verification. 
         [0082]    In the summary of the above descriptions, the present disclosure proposes a method with noise handling, which can identify an optimal measurement mode with more slight electromagnetic interference for proximity detection operation, especially sinusoidal noise interference, and thereby the accuracy of proximity detection operation can be improved. 
         [0083]    While the preferred embodiments of the present invention have been illustrated and described, it will be understood by those skilled in the art that various changes and modifications may be made, and equivalents may be substituted for elements thereof without departing from the true scope of the present invention. Therefore, it is intended that the present invention not be limited to the particular embodiment disclosed as the best mode contemplated for carrying out the present invention; instead, it is intended that the present invention include all embodiments falling within the scope of the appended claims.
The present invention provides a control module and a method operable in a touch-sensitive apparatus for measuring noise, wherein the touch-sensitive apparatus comprises a touch-sensitive module having a plurality of first electrodes and a plurality of second electrodes that intersect in multiple regions of the touch sensitive module, said method comprising the steps of: disconnecting the first electrodes from a driving voltage source; and acquiring a plurality of voltage values of noise by measuring a plurality of voltage signals associated with the second electrodes over a plurality of measurement cycles at a predetermined operating frequency during the first electrodes without a driving voltage.